SNVS847F June   2012  – November 2017 LM34926

PRODUCTION DATA.  

  1. Features
  2. Applications
  3. Description
  4. Revision History
  5. Pin Configuration and Functions
  6. Specifications
    1. 6.1 Absolute Maximum Ratings
    2. 6.2 ESD Ratings
    3. 6.3 Recommended Operating Ratings
    4. 6.4 Thermal Information
    5. 6.5 Electrical Characteristics
    6. 6.6 Switching Characteristics
    7. 6.7 Typical Characteristics
  7. Detailed Description
    1. 7.1 Overview
    2. 7.2 Functional Block Diagram
    3. 7.3 Feature Description
      1. 7.3.1  Control Overview
      2. 7.3.2  VCC Regulator
      3. 7.3.3  Regulation Comparator
      4. 7.3.4  Overvoltage Comparator
      5. 7.3.5  On-Time Generator
      6. 7.3.6  Current Limit
      7. 7.3.7  N-Channel Buck Switch and Driver
      8. 7.3.8  Synchronous Rectifier
      9. 7.3.9  Undervoltage Detector
      10. 7.3.10 Thermal Protection
      11. 7.3.11 Ripple Configuration
      12. 7.3.12 Soft Start
    4. 7.4 Device Functional Modes
  8. Application and Implementation
    1. 8.1 Application Information
    2. 8.2 Typical Application
      1. 8.2.1 Design Requirements
      2. 8.2.2 Detailed Design Procedure
        1. 8.2.2.1  Custom Design With WEBENCH® Tools
        2. 8.2.2.2  Transformer Turns Ratio
        3. 8.2.2.3  Total IOUT
        4. 8.2.2.4  RFB1, RFB2
        5. 8.2.2.5  Frequency Selection
        6. 8.2.2.6  Transformer Selection
        7. 8.2.2.7  Primary Output Capacitor
        8. 8.2.2.8  Secondary Output Capacitor
        9. 8.2.2.9  Type III Feedback Ripple Circuit
        10. 8.2.2.10 Secondary Diode
        11. 8.2.2.11 VCC and Bootstrap Capacitor
        12. 8.2.2.12 Input Capacitor
        13. 8.2.2.13 UVLO Resistors
        14. 8.2.2.14 VCC Diode
      3. 8.2.3 Application Curves
  9. Power Supply Recommendations
  10. 10Layout
    1. 10.1 Layout Guidelines
    2. 10.2 Layout Example
  11. 11Device and Documentation Support
    1. 11.1 Device Support
      1. 11.1.1 Development Support
        1. 11.1.1.1 Custom Design With WEBENCH® Tools
    2. 11.2 Receiving Notification of Documentation Updates
    3. 11.3 Community Resources
    4. 11.4 Trademarks
    5. 11.5 Electrostatic Discharge Caution
    6. 11.6 Glossary
  12. 12Mechanical, Packaging, and Orderable Information

Package Options

Mechanical Data (Package|Pins)
Thermal pad, mechanical data (Package|Pins)
Orderable Information

Application and Implementation

NOTE

Information in the following applications sections is not part of the TI component specification, and TI does not warrant its accuracy or completeness. TI’s customers are responsible for determining suitability of components for their purposes. Customers should validate and test their design implementation to confirm system functionality.

Application Information

The LM34926 device is step-down DC-DC converter. The device is typically used to convert a higher DC voltage to a lower DC voltage with a maximum available output current of 300 mA. Use the following design procedure to select component values for the LM34926 device. Alternately, use the WEBENCH® software to generate a complete design. The WEBENCH software uses an iterative design procedure and accesses a comprehensive database of components when generating a design. This section presents a simplified discussion of the design process.

Typical Application

Application Circuit: 20-V to 95-V Input and 10-V, 250-mA Output Isolated Fly-Buck™ Converter

LM34926 lm34926_ref_sch_SNVS847.gif Figure 12. Isolated Fly-Buck™ Converter Using LM34926

Design Requirements

Selection of external components is illustrated through a design example. Table 3 lists the design example specifications.

Table 3. Buck Converter Design Specifications

DESIGN PARAMETERS VALUE
Input Voltage Range 20 V to 95 V
Primary Output Voltage 10 V
Secondary (Isolated) Output Voltage 9.5 V
Maximum Output Current (Primary + Secondary) 250 mA
Maximum Power Output 2.5 W
Nominal Switching Frequency 750 kHz

Detailed Design Procedure

Custom Design With WEBENCH® Tools

Click here to create a custom design using the LM34926 device with the WEBENCH® Power Designer.

  1. Start by entering the input voltage (VIN), output voltage (VOUT), and output current (IOUT) requirements.
  2. Optimize the design for key parameters such as efficiency, footprint, and cost using the optimizer dial.
  3. Compare the generated design with other possible solutions from Texas Instruments.

The WEBENCH Power Designer provides a customized schematic along with a list of materials with real-time pricing and component availability.

In most cases, these actions are available:

  • Run electrical simulations to see important waveforms and circuit performance
  • Run thermal simulations to understand board thermal performance
  • Export customized schematic and layout into popular CAD formats
  • Print PDF reports for the design, and share the design with colleagues

Get more information about WEBENCH tools at www.ti.com/WEBENCH.

Transformer Turns Ratio

The transformer turns ratio is selected based on the ratio of the primary output voltage to the secondary (isolated) output voltage. In this design example, the two outputs are nearly equal and a 1:1 turns ratio transformer is selected. Therefore, N2 / N1 = 1. If the secondary (isolated) output voltage is significantly higher or lower than the primary output voltage, a turns ratio less than or greater than 1 is recommended. The primary output voltage is normally selected based on the input voltage range such that the duty cycle of the converter does not exceed 50% at the minimum input voltage. This condition is satisfied if VOUT1 < VIN_MIN / 2

Total IOUT

The total primary referred load current is calculated by multiplying the isolated output loads by the turns ratio of the transformer as shown in Equation 6.

Equation 6. LM34926 eq_IOUT_max_SNVS847.gif

RFB1, RFB2

The feedback resistors are selected to set the primary output voltage. The selected value for RFB1 is 1 kΩ. RFB2 can be calculated using the following equations to set VOUT1 to the specified value of 10 V. A standard resistor value of 7.32 kΩ is selected for RFB2.

Equation 7. LM34926 30199835.gif
Equation 8. LM34926 30199836.gif

Frequency Selection

Equation 1 is used to calculate the value of RON required to achieve the desired switching frequency.

Equation 9. LM34926 30199838.gif

where

For VOUT1 of 10 V and fSW of 750 kHz, the calculated value of RON is 148 kΩ. A lower value of 130 kΩ is selected for this design to allow for second-order effects at high switching frequency that are not included in Equation 9.

Transformer Selection

A coupled inductor or a flyback-type transformer is required for this topology. Energy is transferred from primary to secondary when the low-side synchronous switch of the buck converter is conducting.

The maximum inductor primary ripple current that can be tolerated without exceeding the buck switch peak current limit threshold (0.39-A minimum) is given by Equation 10.

Equation 10. LM34926 eq_A_transformer_selection_snvs847.gif

Using the maximum peak-to-peak inductor ripple current ΔIL1 from Equation 10, the minimum inductor value is given by Equation 11.

Equation 11. LM34926 eq_B_transformer_selection_snvs847.gif

A higher value of 47 µH is selected to insure the high-side switch current does not exceed the minimum peak current limit threshold.

Primary Output Capacitor

In a conventional buck converter the output ripple voltage is calculated as shown in Equation 12.

Equation 12. LM34926 30199846.gif

To limit the primary output ripple voltage ΔVOUT1 to approximately 50 mV, an output capacitor COUT1 of 0.93 µF is required.

Figure 13 shows the primary winding current waveform (IL1) of a fly-buck converter. The reflected secondary winding current adds to the primary winding current during the buck switch off-time. Because of this increased current, the output voltage ripple is not the same as in conventional buck converter. The output capacitor value calculated in Equation 12 should be used as the starting point. Optimization of output capacitance over the entire line and load range must be done experimentally. If the majority of the load current is drawn from the secondary isolated output, a better approximation of the primary output voltage ripple is given by Equation 13.

Equation 13. LM34926 eq_primary_out_cap_snvs846.gif
LM34926 30199809.gif Figure 13. Current Waveforms for COUT1 Ripple Calculation

A standard 1-µF, 25-V capacitor is selected for this design. If lower output voltage ripple is required, a higher value should be selected for COUT1 and/or COUT2.

Secondary Output Capacitor

A simplified waveform for secondary output current (IOUT2) is shown in Figure 14.

LM34926 30199810.gif Figure 14. Secondary Current Waveforms for COUT2 Ripple Calculation

The secondary output current (IOUT2) is sourced by COUT2 during on-time of the buck switch, TON. Ignoring the current transition times in the secondary winding, the secondary output capacitor ripple voltage can be calculated using Equation 14.

Equation 14. LM34926 30199848.gif

For a 1:1 transformer turns ratio, the primary and secondary voltage ripple equations are identical. Therefore, COUT2 is chosen to be equal to COUT1 (1 µF) to achieve comparable ripple voltages on primary and secondary outputs.

If lower output voltage ripple is required, a higher value should be selected for COUT1 and/or COUT2.

Type III Feedback Ripple Circuit

Type III ripple circuit as described in Ripple Configuration is required for the Fly-Buck topology. Type I and Type II ripple circuits use series resistance and the triangular inductor ripple current to generate ripple at VOUT and the FB pin. The primary ripple current of a Fly-Buck is the combination or primary and reflected secondary currents as shown in Figure 13. In the fly-buck topology, Type I and Type II ripple circuits suffer from large jitter as the reflected load current affects the feedback ripple.

LM34926 30199811.gif Figure 15. Type III Ripple Circuit

Selecting the Type III ripple components using the equations from Ripple Configuration ensures that the FB pin ripple is be greater than the capacitive ripple from the primary output capacitor COUT1. The feedback ripple component values are chosen as shown in Equation 15.

Equation 15. LM34926 30199849.gif

The calculated value for Rr is 66 kΩ. This value provides the minimum ripple for stable operation. A smaller resistance should be selected to allow for variations in TON, COUT1 and other components. For this design, Rr value of 46.4 kΩ is selected.

Secondary Diode

The reverse voltage across secondary-rectifier diode D1 when the high-side buck switch is off can be calculated using Equation 16.

Equation 16. LM34926 30199845.gif

For a VIN_MAX of 95 V and the 1:1 turns ratio of this design, a 100-V Schottky is selected.

VCC and Bootstrap Capacitor

A 1-µF capacitor of 16-V or higher rating is recommended for the VCC regulator bypass capacitor.

A good value for the BST pin bootstrap capacitor is 0.01-µF with a 16-V or higher rating.

Input Capacitor

The input capacitor is typically a combination of a smaller bypass capacitor located near the regulator IC and a larger bulk capacitor. The total input capacitance should be large enough to limit the input voltage ripple to a desired amplitude. For input ripple voltage ΔVIN, CIN can be calculated using Equation 17.

Equation 17. LM34926 eq015_snvs846.gif

Choosing a ΔVIN of 0.5 V gives a minimum CIN of 0.167 μF. A standard value of 0.1 μF is selected for CBYP in this design. A bulk capacitor of higher value reduces voltage spikes due to parasitic inductance between the power source to the converter. A standard value of 1 μF is selected for CIN in this design. The voltage ratings of the two input capacitors should be greater than the maximum input voltage under all conditions.

UVLO Resistors

UVLO resistors RUV1 and RUV2 set the undervoltage lockout threshold and hysteresis according to Equation 18 and Equation 19.

Equation 18. LM34926 30199839.gif

where

Equation 19. LM34926 30199840.gif

For a UVLO hysteresis of 2.5 V and UVLO rising threshold of 20 V, Equation 18 and Equation 19 require RUV1 of 8.25 kΩ and RUV2 of 127 kΩ and these values are selected for this design example.

VCC Diode

Diode D2 is an optional diode connected between VOUT1 and the VCC regulator output pin. When VOUT1 is more than one diode drop greater than the VCC voltage, the VCC bias current is supplied from VOUT1. This results in reduced power losses in the internal VCC regulator which improves converter efficiency. VOUT1 must be set to a voltage at least one diode drop higher than 8.55 V (the maximum VCC voltage) if D2 is used to supply bias current.

Application Curves

LM34926 app_curve_02_snvs847.gif
VIN = 48 V IOUT1 = 0 mA IOUT2 = 100 mA
Figure 16. Steady-State Waveform
LM34926 app_curve_01_snvs847.gif
VOUT1 = 10 V
Figure 18. Efficiency at 750 kHz
LM34926 app_curve_03_snvs847.gif
VIN = 48 V Step Load on IOUT2 = 80 to 180 mA IOUT1 = 0
Figure 17. Step Load Response