TI’s LMV65x devices are high-performance, low-power operational amplifier ICs implemented with TI's advanced VIP50 process. This family of parts features 12 MHz of bandwidth while consuming only 116 μA of current, which is an exceptional bandwidth to power ratio in this operational amplifier class. The LMV65x devices are unity-gain stable and provide an excellent solution for general-purpose amplification in low-voltage, low-power applications.
This family of low-voltage, low-power amplifiers provides superior performance and economy in terms of power and space usage. These operational amplifiers have a maximum input offset voltage of 1.5 mV, a rail-to-rail output stage, and an input common-mode voltage range that includes ground. The LMV65x provide a PSRR of 95 dB, a CMRR of 100 dB, and a total harmonic distortion (THD) of 0.003% at 1-kHz frequency and 2-kΩ load.
The operating supply voltage range for this family of parts is from 2.7 V and 5.5 V. These operational amplifiers can operate over a wide temperature range (−40°C to 125°C), making them ideal for automotive applications, sensor applications, and portable equipment applications. The LMV651 is offered in the ultra-tiny 5-pin SC70 and 5-pin SOT-23 package. The LMV652 is offered in an 8-pin VSSOP package. The LMV654 is offered in a 14-pin TSSOP package.
PART NUMBER | PACKAGE | BODY SIZE (NOM) |
---|---|---|
LMV651 | SOT-23 (5) | 2.90 mm × 1.60 mm |
SC70 (5) | 2.00 mm × 1.25 mm | |
LMV652 | VSSOP (8) | 3.00 mm × 3.00 mm |
LMV654 | TSSOP (14) | 5.00 mm × 4.40 mm |
Changes from J Revision (March 2013) to K Revision
Changes from I Revision (March 2012) to J Revision
PIN | I/O | DESCRIPTION | |
---|---|---|---|
NAME | NO. | ||
–IN | 3 | I | Inverting Input |
+IN | 1 | I | Noninverting Input |
OUT | 4 | O | Output |
V– | 2 | P | Negative supply input |
V+ | 5 | P | Positive Supply Input |
PIN | I/O | DESCRIPTION | |||
---|---|---|---|---|---|
NAME | VSSOP | TSSOP | |||
–IN A | 2 | 2 | I | Inverting input, channel A | |
+IN A | 3 | 3 | I | Noninverting input, channel A | |
–IN B | 6 | 6 | I | Inverting input, channel B | |
+IN B | 5 | 5 | I | Noninverting input, channel B | |
–IN C | — | 9 | I | Inverting input, channel C | |
+IN C | — | 10 | I | Noninverting input, channel C | |
–IN D | — | 13 | I | Inverting input, channel D | |
+IN D | — | 12 | I | Noninverting input, channel D | |
OUT A | 1 | 1 | O | Output, channel A | |
OUT B | 7 | 7 | O | Output, channel B | |
OUT C | — | 8 | O | Output, channel C | |
OUT D | — | 14 | O | Output, channel D | |
V– | 4 | 11 | P | Negative (lowest) power supply | |
V+ | 8 | 4 | P | Positive (highest) power supply |
MIN | MAX | UNIT | ||
---|---|---|---|---|
Differential input VID | ±0.3 | |||
Supply voltage (VS = V+ - V−) | 6 | |||
Input or output pin voltage | V− − 0.3 | V+ + 0.3 | V | |
Soldering information | Infrared or convection (20 sec) | 235 | °C | |
Wave soldering lead temperature (10 sec) | 260 | |||
Junction temperature(3) | 150 | °C | ||
Storage temperature, Tstg | −65 | 150 | °C |
VALUE | UNIT | |||
---|---|---|---|---|
V(ESD) | Electrostatic discharge | Human-body model (HBM)(1) | ±2000 | V |
Machine model(2) | ±100 |
MIN | MAX | UNIT | ||
---|---|---|---|---|
Temperature | −40 | 125 | °C | |
Supply voltage | 2.7 | 5.5 | V |
THERMAL METRIC(1) | LMV651 | LMV652 | LMV653 | UNIT | ||
---|---|---|---|---|---|---|
DCK (SC70) |
DBV (SOT-23) |
DGK (VSSOP) |
PW (TSSOP) |
|||
5 PINS | 5 PINS | 8 PINS | 14 PINS | |||
RθJA | Junction-to-ambient thermal resistance | 303.5 | 214.2 | 200.3 | 134.9 | °C/W |
RθJC(top) | Junction-to-case (top) thermal resistance | 135.5 | 173.3 | 89.1 | 60.9 | °C/W |
RθJB | Junction-to-board thermal resistance | 81.1 | 72.5 | 120.9 | 77.3 | °C/W |
ψJT | Junction-to-top characterization parameter | 8.4 | 56.7 | 21.7 | 11.5 | °C/W |
ψJB | Junction-to-board characterization parameter | 80.4 | 71.9 | 119.4 | 76.7 | °C/W |
RθJC(bot) | Junction-to-case (bottom) thermal resistance | n/a | n/a | n/a | n/a | °C/W |
PARAMETER | TEST CONDITIONS | MIN(2) | TYP(1) | MAX(2) | UNIT | ||
---|---|---|---|---|---|---|---|
VOS | Input offset voltage | 0.1 | ±1.5 | mV | |||
Over specified temperature range | 2.7 | ||||||
TC VOS | Input offset average drift | 6.6 | μV/°C | ||||
IB | Input bias current(3) | 80 | 120 | nA | |||
IOS | Input offset current | 2.2 | 15 | nA | |||
CMRR | Common-mode rejection ratio | 0 ≤ VCM≤ 2 V | 87 | 100 | dB | ||
Over specified temperature range | 80 | ||||||
PSRR | Power supply rejection ratio | 3 ≤ V+ ≤ 5 V, VCM = 0.5 | 87 | 95 | dB | ||
Over specified temperature range | 81 | ||||||
2.7 ≤ V+ ≤ 5.5 V, VCM = 0.5 |
87 | 95 | |||||
Over specified temperature range | 81 | ||||||
CMVR | Input common-mode voltage range | CMRR ≥ 75 dB | 0 | 2.1 | V | ||
CMRR ≥ 60 dB, over specified temperature range | 0 | 2.1 | |||||
AVOL | Large signal voltage gain | 0.3 ≤ VO ≤ 2.7, RL = 2 kΩ to V+/2 | 80 | 85 | dB | ||
0.4 ≤ VO ≤ 2.6, RL = 2 kΩ to V+/2, over specified temperature range | 76 | ||||||
0.3 ≤ VO ≤ 2.7, RL = 10 kΩ to V+/2 | 86 | 93 | |||||
0.4 ≤ VO ≤ 2.6, RL = 10 kΩ to V+/2, over specified temperature range | 83 | ||||||
VO | Output swing high | RL = 2 kΩ to V+/2 | 80 | 95 | mV from rail | ||
Over specified temperature range | 120 | ||||||
RL = 10 kΩ to V+/2 | 45 | 50 | |||||
Over specified temperature range | 60 | ||||||
Output swing low | RL = 2 kΩ to V+/2 | 95 | 110 | ||||
Over specified temperature range | 125 | ||||||
RL = 10 kΩ to V+/2 | 60 | 65 | |||||
Over specified temperature range | 75 | ||||||
ISC | Maximum continuous output current | Sourcing(4) | 17 | mA | |||
Sinking(4) | 25 | ||||||
IS | Supply current per amplifier | LMV651 | 115 | 140 | μA | ||
Over specified temperature range | 175 | ||||||
LMV652 | 118 | 140 | |||||
Over specified temperature range | 175 | ||||||
LMV654 | 122 | 140 | |||||
Over specified temperature range | 175 | ||||||
SR | Slew rate | AV = +1, 10% to 90%(5) | 3.0 | V/μs | |||
GBW | Gain bandwidth product | 12 | MHz | ||||
en | Input-referred voltage noise | f = 100 kHz | 17 | nV/√Hz | |||
f = 1 kHz | 17 | ||||||
in | Input-referred current noise | f = 100 kHz | 0.1 | pA/√Hz | |||
f = 1 kHz | 0.15 | ||||||
THD | Total harmonic distortion | f = 1 kHz, AV = 2, RL = 2 kΩ | 0.003% |
PARAMETER | TEST CONDITIONS | MIN(2) | TYP(1) | MAX(2) | UNIT | ||
---|---|---|---|---|---|---|---|
VOS | Input offset voltage | 0.1 | ±1.5 | mV | |||
Over specified temperature range | 2.7 | ||||||
TC VOS | Input offset average drift | 6.6 | μV/°C | ||||
IB | Input bias current | See(3) | 80 | 120 | nA | ||
IOS | Input offset current | 2.2 | 15 | nA | |||
CMRR | Common-mode rejection ratio | 0 ≤ VCM≤ 4 V | 90 | 100 | dB | ||
Over specified temperature range | 83 | ||||||
PSRR | Power supply rejection ratio | 3 V ≤ V+ ≤ 5 V, VCM = 0.5 V | 87 | 95 | dB | ||
Over specified temperature range | 81 | ||||||
2.7 V ≤ V+ ≤ 5.5 V, VCM = 0.5 V | 87 | 95 | |||||
Over specified temperature range | 81 | ||||||
CMVR | Input common-mode voltage range | CMRR ≥ 80 dB |
0 | 4.1 | V | ||
CMRR ≥ 68 dB, over specified temperature range | 0 | 4.1 | |||||
AVOL | Large signal voltage gain | 0.3 ≤ VO ≤ 4.7 V, RL = 2 kΩ to V+/2 |
79 | 84 | dB | ||
0.4 ≤ VO ≤ 4.6 V, RL = 2 kΩ to V+/2, over specified temperature range | 76 | ||||||
0.3 ≤ VO ≤ 4.7 V, RL = 10 kΩ to V+/2 |
87 | 94 | |||||
0.4 ≤ VO ≤ 4.6 V, RL = 10 kΩ to V+/2, over specified temperature range | 84 | ||||||
VO | Output swing high | RL = 2 kΩ to V+/2 | 120 | 140 | mV from rail | ||
Over specified temperature range | 185 | ||||||
RL = 10 kΩ to V+/2 | 75 | 90 | |||||
Over specified temperature range | 120 | ||||||
Output swing low | RL = 2 kΩ to V+/2 | 110 | 130 | ||||
Over specified temperature range | 150 | ||||||
RL = 10 kΩ to V+/2 | 70 | 80 | |||||
Over specified temperature range | 95 | ||||||
ISC | Maximum continuous output current | Sourcing(5) | 18.5 | mA | |||
Sinking(5) | 25 | ||||||
IS | Supply current per amplifier | LMV651 | 116 | 140 | μA | ||
Over specified temperature range | 175 | ||||||
LMV652 | 118 | 140 | |||||
Over specified temperature range | 175 | ||||||
LMV654 | 122 | 140 | |||||
Over specified temperature range | 175 | ||||||
SR | Slew rate | AV = +1, VO = 1 VPP, 10% to 90%(4) | 3.0 | V/μs | |||
GBW | Gain bandwidth product | 12 | MHz | ||||
en | Input-referred voltage noise | f = 100 kHz | 17 | nV/√Hz | |||
f = 1 kHz | 17 | ||||||
in | Input-referred current noise | f = 100 kHz | 0.1 | pA/√Hz | |||
f = 1 kHz | 0.15 | ||||||
THD | Total harmonic distortion | f = 1 kHz, AV = 2, RL = 2 kΩ | 0.003% |
TI’s LMV65x devices have 12 MHz of bandwidth, are unity-gain stable, and consume only 116 μA of current. They also have a maximum input offset voltage of 1.5 mV, a rail-to-rail output stage, and an input common-mode voltage range that includes ground. Lastly, these operational amplifiers provide a PSRR of 95 dB, a CMRR of 100 dB, and a total harmonic distortion (THD) of 0.003% at 1-kHz frequency and 2-kΩ load.
The LMV65x have performance specified at supply voltages of 3 V and 5 V. These parts are specified to be operational at all supply voltages between 2.7 V and 5.5 V. The LMV651 draws a low supply current of 116 μA, the LMV652 draws 118 μA/channel and the LMV654 draws 122 μA/channel. This family of operational amplifiers provides the low voltage and low power amplification that is essential for portable applications.
Despite drawing the very low supply current of 116 µA, the LMV65x manage to provide a wide unity-gain bandwidth of 12 MHz. This is easily one of the best bandwidth to power ratios ever achieved, and allows these operational amplifiers to provide wideband amplification while using the minimum amount of power. This makes this family of parts ideal for low-power signal processing applications such as portable media players and other accessories.
The LMV65x provides a flatband input referred voltage noise density of 17 nV/√Hz, which is significantly better than the noise performance expected from a low-power operational amplifiers. These operational amplifiers also feature exceptionally low 1/f noise, with a very low 1/f noise corner frequency of 4 Hz. This makes these parts ideal for low power applications which require decent noise performance, such as PDAs and portable sensors.
The LMV65x each have a rail-to-rail output stage, which provides the maximum possible output dynamic range. This is especially important for applications requiring a large output swing. The input common-mode range of this family of devices includes the negative supply rail which allows direct sensing at ground in a single-supply operation.
The small footprint of the packages for the LMV65x saves space on printed-circuit boards, and enables the design of smaller and more compact electronic products. Long traces between the signal source and the operational amplifier make the signal path susceptible to noise. By using a physically smaller package, these operational amplifiers can be placed closer to the signal source, reducing noise pickup and enhancing signal integrity.
If the phase margin of the LMV65x is plotted with respect to the capacitive load (CL) at its output, it is seen that the phase margin reduces significantly if CL is increased beyond 100 pF. This is because the operational amplifier is designed to provide the maximum bandwidth possible for a low supply current. Stabilizing it for higher capacitive loads would have required either a drastic increase in supply current, or a large internal compensation capacitance, which would have reduced the bandwidth of the operational amplifier. Hence, if these devices are to be used for driving higher capacitive loads, they would have to be externally compensated.
An operational amplifier, ideally, has a dominant pole close to DC, which causes its gain to decay at the rate of 20 dB/decade with respect to frequency. If this rate of decay, also known as the rate of closure (ROC), remains the same until the unity-gain bandwidth of the operational amplifiers is stable. If, however, a large capacitance is added to the output of the operational amplifier, it combines with the output impedance of the operational amplifier to create another pole in its frequency response before its unity-gain frequency (see Figure 34). This increases the ROC to 40 dB/decade and causes instability.
In such a case a number of techniques can be used to restore stability to the circuit. The idea behind all these schemes is to modify the frequency response such that it can be restored to an ROC of 20 dB/decade, which ensures stability.
Figure 35 illustrates a compensation technique, known as in-the-loop compensation, that employs an RC feedback circuit within the feedback loop to stabilize a noninverting amplifier configuration. A small series resistance, RS, is used to isolate the amplifier output from the load capacitance, CL, and a small capacitance, CF, is inserted across the feedback resistor to bypass CL at higher frequencies.
The values for RS and CF are decided by ensuring that the zero attributed to CF lies at the same frequency as the pole attributed to CL. This ensures that the effect of the second pole on the transfer function is compensated for by the presence of the zero, and that the ROC is maintained at 20 dB/decade. For the circuit shown in Figure 35 the values of RS and CF are given by Equation 1. Values of RS and CF required for maintaining stability for different values of CL, as well as the phase margins obtained, are shown in Table 1. RF and RIN are taken to be 10 kΩ, RL is 2 kΩ, while ROUT is taken as 340 Ω.
CL (pF) | RS (Ω) | CF (pF) | PHASE MARGIN (°) |
---|---|---|---|
150 | 340 | 15 | 39.4 |
200 | 340 | 20 | 34.6 |
250 | 340 | 25 | 31.1 |
Although this methodology provides circuit stability for any load capacitance, it does so at the price of bandwidth. The closed-loop bandwidth of the circuit is now limited by RF and CF.
In some applications, it is essential to drive a capacitive load without sacrificing bandwidth. In such a case, in the loop compensation is not viable. A simpler scheme for compensation is shown in Figure 36. A resistor, RISO, is placed in series between the load capacitance and the output. This introduces a zero in the circuit transfer function, which counteracts the effect of the pole formed by the load capacitance, and ensures stability. The value of RISO to be used should be decided depending on the size of CL and the level of performance desired. Values ranging from 5 Ω to 50 Ω are usually sufficient to ensure stability. A larger value of RISO results in a system with lesser ringing and overshoot, but it also limits the output swing and the short-circuit current of the circuit.
NOTE
Information in the following applications sections is not part of the TI component specification, and TI does not warrant its accuracy or completeness. TI’s customers are responsible for determining suitability of components for their purposes. Customers should validate and test their design implementation to confirm system functionality.
With a low supply current, low power operation, and low harmonic distortion, the LMV65x devices are ideal for wide-bandwidth, high gain amplification.
The wide unity-gain bandwidth allows these parts to provide large gain over a wide frequency range, while driving loads as low as 2 kΩ with less than 0.003% distortion.
Figure 37 is an inverting amplifier, with a 100-kΩ feedback resistor, R2, and a 1-kΩ input resistor, R1, and provides a gain of −100. With the LMV65x, these circuits can provide gain of −100 with a −3-dB bandwidth of 120 kHz, for a quiescent current as low as 116 μA. Coupling capacitors CC1 and CC2 can be added to isolate the circuit from DC voltages, while RB1 and RB2 provide DC biasing. A feedback capacitor CF can also be added to improve compensation.
With a low supply current, low power operation, and low harmonic distortion, the LMV65x devices are ideal for wide-bandwidth, high gain amplification. The wide unity-gain bandwidth allows these parts to provide large gain over a wide frequency range, while driving loads as low as 2 kΩ with less than 0.003% distortion. Figure 39 is a noninverting amplifier with a gain of 1001, can provide that gain with a −3-dB bandwidth of 12 kHz, for a similar low quiescent power dissipation. With the LMV65x, these circuits can provide gain of −100 with a −3-dB bandwidth of 120 kHz, for a quiescent current as low as 116 μA. Coupling capacitors CC1 and CC2 can be added to isolate the circuit from DC voltages, while RB1 and RB2 provide DC biasing. A feedback capacitor CF can also be added to improve compensation.
With a wide unity-gain bandwidth of 12 MHz, low input-referred noise density, and a low power supply current, the LMV65x devices are well suited for low-power filtering applications. Active filter topologies, like the Sallen-Key low-pass filter shown in Figure 40, are very versatile, and can be used to design a wide variety of filters (Chebyshev, Butterworth, or Bessel). The Sallen-Key topology, in particular, can be used to attain a wide range of Q, by using positive feedback to reject the undesired frequency range.
In the circuit shown in Figure 40, the two capacitors appear as open circuits at lower frequencies and the signal is simply buffered to the output. At high frequencies the capacitors appear as short circuits and the signal is shunted to ground by one of the capacitors before it can be amplified. Near the cutoff frequency, where the impedance of the capacitances is on the same order as Rg and Rf, positive feedback through the other capacitor allows the circuit to attain the desired Q. The ratio of the two resistors, m2, provides a knob to control the value of Q obtained.
Do properly bypass the power supplies.
Do add series resistence to the output when driving capacitive loads, particularly cables, Muxes, and ADC inputs.
Do add series current limiting resistors and external Schottky clamp diodes if input voltage is expected to exceed the supplies. Limit the current to 1 mA or less (1 kΩ per volt).
For proper operation, the power supplies must be properly decoupled. For decoupling the supply lines, TI recommends that 10-nF capacitors be placed as close as possible to the operational amplifier power supply pins. For single supply, place a capacitor between V+ and V– supply leads. For dual supplies, place one capacitor between V+ and ground, and one capacitor between V– and ground.