SGLS276D January 2005 – March 2016 TPS61040-Q1 , TPS61041-Q1
PRODUCTION DATA.
Refer to the PDF data sheet for device specific package drawings
The TPS6104x-Q1 devices are high-frequency boost converters for automotive applications. The devices are ideal for generating output voltages up to 28 V from a pre-regulated low voltage rail, dual-cell NiMH/NiCd or a single-cell Li-Ion battery, supporting input voltages from 1.8 V to 6 V.
The TPS6104x-Q1 devices operate with a switching frequency up to 1 MHz, allowing the use of small external components such as ceramic as well as tantalum output capacitors. Combined with the space-saving, 5-pin SOT-23 package, the TPS6104x-Q1 devices accomplish a small overall solution size. The TPS61040-Q1 device has an internal 400-mA switch current limit, while the TPS61041-Q1 device has a 250-mA switch current limit, offering lower output voltage ripple and allowing the use of a smaller form factor inductor for lower-power applications.
The TPS6104x-Q1 devices operate in a pulse frequency modulation (PFM) scheme with constant peak current control. The combination of low quiescent current (28 µA typical) and the optimized control scheme enable operation of the devices at high efficiencies over the entire load current range.
PART NUMBER | PACKAGE | BODY SIZE (NOM) |
---|---|---|
TPS6104x-Q1 | SOT-23 (5) | 2.90 mm × 1.60 mm |
Changes from C Revision (April 2012) to D Revision
Changes from B Revision (July 2011) to C Revision
PIN | I/O | DESCRIPTION | |
---|---|---|---|
NAME | NO. | ||
EN | 4 | I | This is the enable pin of the device. Pulling this pin to ground forces the device into shutdown mode reducing the supply current to less than 1 µA. This pin must not be left floating and must be terminated. |
FB | 3 | I | This is the feedback pin of the device. Connect this pin to the external voltage divider to program the desired output voltage. |
GND | 2 | — | Ground |
SW | 1 | I | Connect the inductor and the Schottky diode to this pin. This is the switch pin and is connected to the drain of the internal power MOSFET. |
VIN | 5 | I | Supply voltage pin |
MIN | MAX | UNIT | ||
---|---|---|---|---|
Supply voltages on pin VIN (2) | –0.3 | 7 | V | |
Voltages on pins EN, FB (2) | –0.3 | VIN + 0.3 | V | |
Switch voltage on pin SW (2) | 30 | V | ||
Continuous power dissipation | See Thermal Information | |||
TJ | Operating junction temperature | –40 | 150 | °C |
TStg | Storage temperature | –65 | 150 | °C |
VALUE | UNIT | |||
---|---|---|---|---|
V(ESD) | Electrostatic discharge | Human-body model (HBM), per AEC Q100-002(1) | ±2000 | V |
Charged-device model (CDM), per AEC Q100-011 | ±750 |
MIN | TYP | MAX | UNIT | ||
---|---|---|---|---|---|
VIN | Input voltage | 1.8 | 6 | V | |
VOUT | Output voltage | 28 | V | ||
L | Inductor(1) | 2.2 | 10 | 47 | μH |
f | Switching frequency(1) | 1 | MHz | ||
CIN | Input capacitor (1) | 4.7 | μF | ||
COUT | Output capacitor (1) | 1 | μF | ||
TA | Operating ambient temperature | –40 | 125 | °C |
THERMAL METRIC(1) | TPS6104x-Q1 | UNIT | |
---|---|---|---|
DBV (SOT-23) | |||
5 PINS | |||
RθJA | Junction-to-ambient thermal resistance | 153.5 | °C/W |
RθJC(top) | Junction-to-case (top) thermal resistance | 105.7 | °C/W |
RθJB | Junction-to-board thermal resistance | 33.5 | °C/W |
ψJT | Junction-to-top characterization parameter | 9.8 | °C/W |
ψJB | Junction-to-board characterization parameter | 33.1 | °C/W |
PARAMETER | TEST CONDITIONS | MIN | TYP | MAX | UNIT | ||
---|---|---|---|---|---|---|---|
SUPPLY CURRENT | |||||||
VIN | Input voltage range | 1.8 | 6 | V | |||
IQ | Operating quiescent current | IOUT = 0 mA, not switching, VFB = 1.3 V | 28 | 50 | μA | ||
ISD | Shutdown current | EN = GND | 0.1 | 1 | μA | ||
VUVLO | Undervoltage lockout threshold | 1.5 | 1.7 | V | |||
ENABLE | |||||||
VIH | EN high level input voltage | 1.3 | V | ||||
VIL | EN low level input voltage | 0.4 | V | ||||
II | EN input leakage current | EN = GND or VIN | 0.1 | 1 | μA | ||
POWER SWITCH AND CURRENT LIMIT | |||||||
Vsw | Maximum switch voltage | 30 | V | ||||
toff | Minimum OFF time | 250 | 400 | 550 | ns | ||
ton | Maximum ON time | 4 | 6 | 7.5 | μs | ||
RDS(on) | MOSFET ON-resistance | VIN = 2.4 V; ISW = 200 mA; TPS61040-Q1 | 600 | 1100 | mΩ | ||
RDS(on) | MOSFET ON-resistance | VIN = 2.4 V; ISW = 200 mA; TPS61041-Q1 | 750 | 1300 | mΩ | ||
MOSFET leakage current | VSW = 28 V | 1 | 10 | μA | |||
ILIM | MOSFET current limit | TPS61040-Q1 | 325 | 400 | 500 | mA | |
ILIM | MOSFET current limit | TPS61041-Q1 | 200 | 250 | 325 | mA | |
OUTPUT | |||||||
VOUT | Adjustable output voltage range(2) | VIN | 28 | V | |||
Vref | Internal voltage reference | 1.233 | V | ||||
IFB | Feedback input bias current | VFB = 1.3 V | 1 | μA | |||
VFB | Feedback trip point voltage | 1.8 V ≤ VIN ≤ 6 V | TJ = –40°C to 85°C | 1.208 | 1.233 | 1.258 | V |
TJ = –40°C to 125°C | 1.2 | 1.233 | 1.27 | ||||
Line regulation (1) | 1.8 V ≤ VIN ≤ 6 V; VOUT = 18 V; Iload = 10 mA; CFF = not connected |
0.05 | %/V | ||||
Load regulation(1) | VIN = 2.4 V; VOUT = 18 V; 0 mA ≤ IOUT ≤ 30 mA | 0.15 | %/mA |
FIGURE | |||
---|---|---|---|
η | Efficiency | vs Load current | Figure 1, Figure 2, Figure 3 |
vs Input voltage | Figure 4 | ||
IQ | Quiescent current | vs Input voltage and temperature | Figure 5 |
VFB | Feedback voltage | vs Temperature | Figure 6 |
ISW | Switch current limit | vs Temperature | Figure 7 |
ICL | Switch current limit | vs Supply voltage, TPS61041-Q1 | Figure 8 |
vs Supply voltage, TPS61040-Q1 | Figure 9 | ||
RDS(on) | RDS(on) | vs Temperature | Figure 10 |
vs Supply voltage | Figure 11 | ||
Line transient response | Figure 13 | ||
Load transient response | Figure 14 | ||
Start-up behavior | Figure 15 |
The TPS6104x-Q1 is a high-frequency boost converter dedicated for small-to-medium LCD bias supply and white-LED backlight supplies. The device is ideal for generating output voltages up to 28 V from a dual-cell NiMH/NiCd or a single-cell device Li-Ion battery.
The internal switch turns on until the inductor current reaches the typical DC current limit (ILIM) of 400 mA (TPS61040-Q1) or 250 mA (TPS61041-Q1). Due to the internal propagation delay of typical 100 ns, the actual current exceeds the DC-current limit threshold by a small amount. The typical peak current limit can be calculated:
where
The higher the input voltage and the lower the inductor value, the greater the peak.
By selecting the TPS6104x-Q1, it is possible to tailor the design to the specific application current limit requirements. A lower current limit supports applications requiring lower output power and allows the use of an inductor with a lower current rating and a smaller form factor. A lower current limit usually has a lower output-voltage ripple as well.
All inductive step-up converters exhibit high inrush current during start-up if no special precaution is made. This can cause voltage drops at the input rail during start-up and may result in an unwanted or early system shutdown.
The TPS6104x-Q1 limits this inrush current by increasing the current limit in two steps starting from for 256 cycles to
for the next 256 cycles, and then full current limit (see Figure 15).
Pulling the enable (EN) to ground shuts down the device reducing the shutdown current to 1 µA (typical). Because there is a conductive path from the input to the output through the inductor and Schottky diode, the output voltage is equal to the input voltage during shutdown. The enable pin must be terminated and must not be left floating. Using a small external transistor disconnects the input from the output during shutdown as shown in Figure 17.
An undervoltage lockout prevents misoperation of the device at input voltages below typical 1.5 V. When the input voltage is below the undervoltage threshold the main switch is turned off.
An internal thermal shutdown is implemented and turns off the internal MOSFETs when the typical junction temperature of 168°C is exceeded. The thermal shutdown has a hysteresis of typically 25°C. This data is based on statistical means and is not tested during the regular mass production of the IC.
The TPS6104x-Q1 operates with an input voltage range of 1.8 V to 6 V and can generate output voltages up to 28 V. The device operates in a pulse frequency modulation (PFM) scheme with constant peak current control. This control scheme maintains high efficiency over the entire load current range, and with a switching frequency up to 1 MHz, the device enables the use of very small external components.
The converter monitors the output voltage, and as soon as the feedback voltage falls below the reference voltage of typically 1.233 V, the internal switch turns on and the current ramps up. The switch turns off as soon as the inductor current reaches the internally set peak current of typically 400 mA (TPS61040-Q1) or 250 mA (TPS61041-Q1). See Peak Current Control for more information. The second criteria that turns off the switch is the maximum ON-time of 6 µs (typical). This is just to limit the maximum ON-time of the converter to cover for extreme conditions. As the switch is turned off, the external Schottky diode is forward biased delivering the current to the output. The switch remains off for a minimum of 400 ns (typical), or until the feedback voltage drops below the reference voltage again. Using this PFM peak-current control scheme, the converter operates in discontinuous conduction mode (DCM) where the switching frequency depends on the output current, which results in high efficiency over the entire load current range. This regulation scheme is inherently stable, allowing a wider selection range for the inductor and output capacitor.
NOTE
Information in the following applications sections is not part of the TI component specification, and TI does not warrant its accuracy or completeness. TI’s customers are responsible for determining suitability of components for their purposes. Customers should validate and test their design implementation to confirm system functionality.
The TPS6104x-Q1 is designed for output voltages up to 28 V with an input voltage range of 1.8 V to 6 V. TPS61040-Q1 can operate up to 400-mA typical peak load current and TPS61040-Q1 can operate up to 250-mA typical peak load current. The device operates in a pulse-frequency-modulation (PFM) scheme with constant peak-current control. This control scheme maintains high efficiency over the entire load current range, and with a switching frequency up to 1 MHz, the device enables the use of very small external components.
The following section provides a step-by-step design approach for configuring the TPS61040-Q1 as a voltage-regulating boost converter for LCD bias supply, as shown in Figure 12.
Table 2 lists the design parameters for this example.
DESIGN PARAMETER | EXAMPLE VALUE |
---|---|
Input Voltage | 1.8 V to 6 V |
Output Voltage | 18 V |
Output Current | 10 mA |
Because the PFM peak-current control scheme is inherently stable, the inductor value does not affect the stability of the regulator. The selection of the inductor together with the nominal load current, input and output voltage of the application determines the switching frequency of the converter. Depending on the application, TI recommends inductor values from 2.2 µH to 47 µH. The maximum inductor value is determined by the maximum ON-time of the switch, typically 6 µs. The peak current limit of 400 mA (typically) must be reached within this
6-µs period for proper operation.
The inductor value determines the maximum switching frequency of the converter. Therefore, select the inductor value that ensures the maximum switching frequency at the converter maximum load current is not exceeded. The maximum switching frequency is calculated using Equation 2.
where
If the selected inductor value does not exceed the maximum switching frequency of the converter, the next step is to calculate the switching frequency at the nominal load current using Equation 3:
where
A smaller inductor value gives a higher converter switching frequency, but lowers the efficiency.
The inductor value has less effect on the maximum available load current and is only of secondary order. The best way to calculate the maximum available load current under certain operating conditions is to estimate the expected converter efficiency at the maximum load current. This number can be taken out of the efficiency graphs shown in Figure 1, Figure 2, Figure 3, and Figure 4. The maximum load current can then be estimated using Equation 4.
where
The maximum load current of the converter is the current at the operation point where the converter starts to enter the continuous conduction mode. Usually the converter should always operate in discontinuous conduction mode.
Last, the selected inductor must have a saturation current that exceeds the maximum peak current of the converter (as calculated in Peak Current Control). Use the maximum value for ILIM for this calculation.
Another important inductor parameter is the DC resistance. The lower the DC resistance, the higher the efficiency of the converter. Table 3 lists few typical inductors for LCD Bias Supply design (see Figure 12), but customers must verify and validate them to check whether they are suitable for their application.
The output voltage is calculated as:
For battery-powered applications, a high impedance voltage divider must be used with a typical value for R2 of ≤200 kΩ and a maximum value for R1 of 2.2 MΩ. Smaller values can be used to reduce the noise sensitivity of the feedback pin.
A feed-forward capacitor across the upper feedback resistor R1 is required to provide sufficient overdrive for the error comparator. Without a feed-forward capacitor, or one whose value is too small, the TPS6104x-Q1 shows double pulses or a pulse burst instead of single pulses at the switch node (SW), causing higher output voltage ripple. If this higher output voltage ripple is acceptable, the feed-forward capacitor can be left out.
The lower the switching frequency of the converter, the larger the feed-forward capacitor value required. A good starting point is to use a 10-pF feed-forward capacitor. As a first estimation, the required value for the feed-forward capacitor at the operation point can also be calculated using Equation 6.
where
The larger the feed-forward capacitor the worse the line regulation of the device. Therefore, when concern for line regulation is paramount, the selected feed-forward capacitor must be as small as possible. See the next section for more information about line and load regulation.
The line regulation of the TPS6104x-Q1 depends on the voltage ripple on the feedback pin. Usually a 50-mV peak-to-peak voltage ripple on the feedback pin FB gives good results.
Some applications require a very tight line regulation and can only allow a small change in output voltage over a certain input voltage range. If no feed-forward capacitor CFF is used across the upper resistor of the voltage feedback divider, the device has the best line regulation. Without the feed-forward capacitor the output voltage ripple is higher because the TPS6104x-Q1 shows output voltage bursts instead of single pulses on the switch pin (SW), increasing the output voltage ripple. Increasing the output capacitor value reduces the output voltage ripple.
If a larger output capacitor value is not an option, a feed-forward capacitor CFF can be used as described in the previous section. The use of a feed-forward capacitor increases the amount of voltage ripple present on the feedback pin (FB). The greater the voltage ripple on the feedback pin (≥50 mV), the worse the line regulation. There are two ways to improve the line regulation further:
For best output voltage filtering, TI recommends a low ESR output capacitor. Ceramic capacitors have a low ESR value but tantalum capacitors can be used as well, depending on the application.
Assuming the converter does not show double pulses or pulse bursts on the switch node (SW), the output voltage ripple can be calculated using Equation 7.
where
Table 4 lists few typical capacitors for LCD Bias Supply design (see Figure 12), but customers must verify and validate them to check whether they are suitable for their application.
DEVICE | CAPACITOR | VOLTAGE RATING | COMPONENT SUPPLIER | COMMENTS |
---|---|---|---|---|
TPS6104x-Q1 | 4.7 μF/X5R/0805 | 6.3 V | Taiyo Yuden JMK212BY475MG | CIN |
10 μF/X5R/0805 | 6.3 V | Taiyo Yuden JMK212BJ106MG | CIN | |
1 μF/X7R/1206 | 25 V | Taiyo Yuden TMK316BJ105KL | COUT | |
1 μF/X5R/1206 | 35 V | Taiyo Yuden GMK316BJ105KL | COUT | |
4.7 μF/X5R/1210 | 25 V | Taiyo Yuden TMK325BJ475MG | COUT |
For good input voltage filtering, TI recommends low-ESR ceramic capacitors. A 4.7-μF ceramic input capacitor is sufficient for most of the applications. For better input voltage filtering this value can be increased. See Table 4 and the Typical Application section for input capacitor recommendations.
To achieve high efficiency, a Schottky diode must be used. The current rating of the diode must meet the peak current rating of the converter as it is calculated in the section peak current control. Use the maximum value for ILIM for this calculation. Table 5 lists the few typical Schottky Diodes for LCD Bias Supply design shown in Figure 12. Customers must verify and validate them, however, to check whether they are suitable for their application.
DEVICE | REVERSE VOLTAGE | COMPONENT SUPPLIER | COMMENTS |
---|---|---|---|
TPS6104x-Q1 | 30 V | ON Semiconductor MBR0530 | |
20 V | ON Semiconductor MBR0520 | ||
20 V | ON Semiconductor MBRM120L | High efficiency | |
30 V | Toshiba CRS02 |
Figure 16 to Figure 22 shows the different possible power supply designs with the TPS6104x-Q1 devices. However, these circuits must be fully validated and tested by customers before they actually use them in their designs. TI does not warrant the accuracy or completeness of these circuits, nor does TI accept any responsibility for them.
The device is designed to operate from an input voltage supply range from 1.8 V to 6 V. The output current of the input power supply must be rated according to the supply voltage, output voltage, and output current of TPS6104x-Q1.
Typical for all switching power supplies, the layout is an important step in the design; especially at high peak currents and switching frequencies. If the layout is not carefully done, the regulator can show noise problems and duty cycle jitter.
Figure 23 provides an example of layout design with TPS6104x-Q1 device.
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PARTS | PRODUCT FOLDER | SAMPLE & BUY | TECHNICAL DOCUMENTS | TOOLS & SOFTWARE | SUPPORT & COMMUNITY |
---|---|---|---|---|---|
TPS61040-Q1 | Click here | Click here | Click here | Click here | Click here |
TPS61041-Q1 | Click here | Click here | Click here | Click here | Click here |
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