Table 2. Design Parameters

8.2.2.1 Inductor Selection, Maximum Load Current

Because the PFM peak-current control scheme is inherently stable, the inductor value does not affect the stability of the regulator. The selection of the inductor together with the nominal load current, input and output voltage of the application determines the switching frequency of the converter. Depending on the application, TI recommends inductor values from 2.2 µH to 47 µH. The maximum inductor value is determined by the maximum ON-time of the switch, typically 6 µs. The peak current limit of 400 mA (typically) must be reached within this
6-µs period for proper operation.

The inductor value determines the maximum switching frequency of the converter. Therefore, select the inductor value that ensures the maximum switching frequency at the converter maximum load current is not exceeded. The maximum switching frequency is calculated using Equation 2.

Equation 2.

where

• I_P = Peak current as described in Peak Current Control
• L = Selected inductor value
• V_IN(min) = The highest switching frequency occurs at the minimum input voltage

If the selected inductor value does not exceed the maximum switching frequency of the converter, the next step is to calculate the switching frequency at the nominal load current using Equation 3:

Equation 3.

where

• I_P = Peak current as described in Peak Current Control
• L = Selected inductor value
• I_load = Nominal load current
• V_d = Rectifier diode forward voltage (typically 0.3 V)

A smaller inductor value gives a higher converter switching frequency, but lowers the efficiency.

The inductor value has less effect on the maximum available load current and is only of secondary order. The best way to calculate the maximum available load current under certain operating conditions is to estimate the expected converter efficiency at the maximum load current. This number can be taken out of the efficiency graphs shown in Figure 1, Figure 2, Figure 3, and Figure 4. The maximum load current can then be estimated using Equation 4.

Equation 4.

where

• I_P = Peak current as described in Peak Current Control
• L = Selected inductor value
• f_S(max) = Maximum switching frequency as calculated previously
• η = Expected converter efficiency. Typically 70% to 85%.

The maximum load current of the converter is the current at the operation point where the converter starts to enter the continuous conduction mode. Usually the converter should always operate in discontinuous conduction mode.

Last, the selected inductor must have a saturation current that exceeds the maximum peak current of the converter (as calculated in Peak Current Control). Use the maximum value for I_LIM for this calculation.

Another important inductor parameter is the DC resistance. The lower the DC resistance, the higher the efficiency of the converter. Table 3 lists few typical inductors for LCD Bias Supply design (see Figure 12), but customers must verify and validate them to check whether they are suitable for their application.

8.2.2.2 Setting The Output Voltage and Feed-Forward Capacitor

The output voltage is calculated as:

Equation 5.

For battery-powered applications, a high impedance voltage divider must be used with a typical value for R2 of ≤200 kΩ and a maximum value for R1 of 2.2 MΩ. Smaller values can be used to reduce the noise sensitivity of the feedback pin.

A feed-forward capacitor across the upper feedback resistor R1 is required to provide sufficient overdrive for the error comparator. Without a feed-forward capacitor, or one whose value is too small, the TPS6104x-Q1 shows double pulses or a pulse burst instead of single pulses at the switch node (SW), causing higher output voltage ripple. If this higher output voltage ripple is acceptable, the feed-forward capacitor can be left out.

The lower the switching frequency of the converter, the larger the feed-forward capacitor value required. A good starting point is to use a 10-pF feed-forward capacitor. As a first estimation, the required value for the feed-forward capacitor at the operation point can also be calculated using Equation 6.

Equation 6.

where

• R1 = Upper resistor of voltage divider
• f_S = Switching frequency of the converter at the nominal load current (see Inductor Selection, Maximum Load Current for calculating the switching frequency)
• C_FF = Choose a value that comes closest to the result of the calculation

The larger the feed-forward capacitor the worse the line regulation of the device. Therefore, when concern for line regulation is paramount, the selected feed-forward capacitor must be as small as possible. See the next section for more information about line and load regulation.

8.2.2.3 Line and Load Regulation

The line regulation of the TPS6104x-Q1 depends on the voltage ripple on the feedback pin. Usually a 50-mV peak-to-peak voltage ripple on the feedback pin FB gives good results.

Some applications require a very tight line regulation and can only allow a small change in output voltage over a certain input voltage range. If no feed-forward capacitor C_FF is used across the upper resistor of the voltage feedback divider, the device has the best line regulation. Without the feed-forward capacitor the output voltage ripple is higher because the TPS6104x-Q1 shows output voltage bursts instead of single pulses on the switch pin (SW), increasing the output voltage ripple. Increasing the output capacitor value reduces the output voltage ripple.

If a larger output capacitor value is not an option, a feed-forward capacitor C_FF can be used as described in the previous section. The use of a feed-forward capacitor increases the amount of voltage ripple present on the feedback pin (FB). The greater the voltage ripple on the feedback pin (≥50 mV), the worse the line regulation. There are two ways to improve the line regulation further:

1. Use a smaller inductor value to increase the switching frequency which will lower the output voltage ripple, as well as the voltage ripple on the feedback pin.
2. Add a small capacitor from the feedback pin (FB) to ground to reduce the voltage ripple on the feedback pin down to 50 mV again. As a starting point, the same capacitor value as selected for the feed-forward capacitor C_FF can be used.

8.2.2.4 Output Capacitor Selection

For best output voltage filtering, TI recommends a low ESR output capacitor. Ceramic capacitors have a low ESR value but tantalum capacitors can be used as well, depending on the application.

Assuming the converter does not show double pulses or pulse bursts on the switch node (SW), the output voltage ripple can be calculated using Equation 7.

Equation 7.

where

• I_P = Peak current as described in the Peak Current Control section
• L = Selected inductor value
• I_out = Nominal load current
• f_S (I_out) = Switching frequency at the nominal load current as calculated previously
• V_d = Rectifier diode forward voltage (typically 0.3 V)
• C_out = Selected output capacitor
• ESR = Output capacitor ESR value

Table 4 lists few typical capacitors for LCD Bias Supply design (see Figure 12), but customers must verify and validate them to check whether they are suitable for their application.

8.2.2.5 Input Capacitor Selection

For good input voltage filtering, TI recommends low-ESR ceramic capacitors. A 4.7-μF ceramic input capacitor is sufficient for most of the applications. For better input voltage filtering this value can be increased. See Table 4 and the Typical Application section for input capacitor recommendations.

8.2.2.6 Diode Selection

To achieve high efficiency, a Schottky diode must be used. The current rating of the diode must meet the peak current rating of the converter as it is calculated in the section peak current control. Use the maximum value for I_LIM for this calculation. Table 5 lists the few typical Schottky Diodes for LCD Bias Supply design shown in Figure 12. Customers must verify and validate them, however, to check whether they are suitable for their application.