Figure 7-2 shows a simplified flyback convertor with the main output-regulation blocks of the device shown, along with typical implementation of secondary-side-derived regulation. The power-train operation is the same as any DCM-flyback circuit. A feedback current is optically coupled to the controller from a shunt-regulator sensing the output voltage.

Figure 7-2 Simplified Flyback Convertor (With the Main Voltage Regulation Blocks)

In this configuration, a secondary-side shunt-regulator, such as the TL431, generates a current through the input photo-diode of an optocoupler. The photo-transistor delivers a proportional current that is dependent on the current-transfer ratio (CTR) of the optocoupler to the FB input of the UCC28740-Q1 controller. This FB current then converts into the V_CL by the input-mirror network, detailed in the device block diagram (see Section 7.2). Output-voltage variations convert to FB-current variations. The FB-current variations modify the V_CL which dictates the appropriate I_PP and f_SW necessary to maintain CV regulation. At the same time, the VS input senses the auxiliary winding voltage during the transfer of transformer energy to the secondary output to monitor for an output overvoltage condition. When f_SW reaches the target maximum frequency, chosen between 32 kHz and 100 kHz, CC operation is entered and further increases in V_CL have no effect.

Figure 7-3 shows that as the secondary current decreases to zero, a clearly defined down slope reflects the decreasing rectifier V_F combined with stray resistance voltage-drop (I_SR_S). To achieve an accurate representation of the secondary output voltage on the auxiliary winding, the discriminator reliably blocks the leakage-inductance reset and ringing while continuously sampling the auxiliary voltage during the down slope after the ringing diminishes. The discriminator then captures the voltage signal at the moment that the secondary-winding current reaches zero. The internal overvoltage threshold on VS is 4.6 V. Temperature compensation of –0.8 mV/°C on the overvoltage threshold offsets the change in the output-rectifier forward voltage with temperature. The resistor divider is selected as outlined in the VS pin description (see Section 7.3.1).

Figure 7-3 Auxiliary-Winding Voltage

The UCC28740-Q1 VS-signal sampler includes signal-discrimination methods to ensure an accurate sample of the output voltage from the auxiliary winding. Controlling some details of the auxiliary-winding signal to ensure reliable operation is necessary; specifically, the reset time of the leakage inductance and the duration of any subsequent leakage-inductance ringing. See Figure 7-4 for a detailed illustration of waveform criteria to ensure a reliable sample on the VS pin.

The first detail to examine is the duration of the leakage-inductance reset pedestal, t_{LK_RESET}, in Figure 7-4. Because t_{LK_RESET} mimics the waveform of the secondary-current decay, followed by a sharp downslope, t_{LK_RESET} is internally blanked for a duration which scales with the peak primary current. Keeping the leakage-reset time to less than 600 ns for I_PP(min), and less than 2.2 µs for I_PP(max) is important.

The second detail is the amplitude of ringing on the V_AUX waveform following t_{LK_RESET}. The peak-to-peak voltage variation at the VS pin must be less than 100 mVp-p for at least 200 ns before the end of the demagnetization time (t_DM). A concern with excessive ringing usually occurs during light or no-load conditions, when t_DM is at the minimum. The tolerable ripple on VS is scaled up to the auxiliary-winding voltage by R_S1 and R_S2, and is equal to 100 mV × (R_S1 + R_S2) / R_S2 .

Figure 7-4 Auxiliary-Winding Waveform Details

During voltage regulation, the controller operates in frequency-modulation mode and amplitude-modulation mode, as shown in Figure 7-5. The internal operating-frequency limits of the device are 100 kHz and f_SW(min). The maximum operating frequency of the converter at full-load is generally chosen to be slightly lower than 100 kHz to allow for tolerances, or significantly lower due to switching-loss considerations. The maximum operating frequency and primary peak current chosen determine the transformer primary inductance of the converter. The shunt-regulator bias power, output preload resistor (if any), and low-power conversion efficiency determine the minimum-operating frequency of the converter. Voltage-loop stability compensation is applied at the shunt-regulator which drives the opto-coupled feedback signal. The tolerances chosen for the shunt-regulator reference and the sense resistors determines the regulation accuracy.

Figure 7-5 Frequency and Amplitude Modulation Modes (During CV Regulation)

The level of feedback current (I_FB) into the FB pin determines the internal V_CL which determines the operating point of the controller while in CV mode. When I_FB rises above 22 µA, no further decrease in f_SW occurs. When the output-load current increases to the point where maximum f_SW is reached, control transfers to CC mode. All current, voltage, frequency, breakpoints, and curve-segment linearity depicted in Figure 7-5 are nominal. Figure 7-5 indicates the general operation of the controller while in CV mode, although minor variations may occur from part to part. An internal frequency-dithering mechanism is enabled when I_FB is less than 14.6 µA to help reduce conducted EMI (including during CC-mode operation), and is disabled otherwise.