Table 7-2 Input Characteristics

Table 7-3 Output Characteristics

7.2.2.1 PCMC (Peak Current Mode Control) PSFB (Phase Shifted Full Bridge) Hardware Configuration Overview

The hardware configuration of the UCD3138x PCMC PSFB converter contains two critical elements that are highlighted in the subsequent sections.

• DPWM initialization - This section will highlight the key register settings and considerations necessary for the UCD3138x to generate the correct MOSFET waveforms for this topology. This maintains the proper phase relationship between the MOSFETs and synchronous rectifiers as well as the proper set up required to function correctly with PCMC.
• PCMC initialization - This section will discuss the register settings and hardware considerations necessary to modulate the DPWM pins with PCMC and internal slope compensation.

7.2.2.2 DPWM Initialization for PSFB

The UCD3138x DPWM peripheral provides flexibility for a wide range of topologies. The PSFB configuration utilizes the Intra-Mux and Edge Generation Modules of the DPWM. For a diagram showing these modules, see the UCD3138x Digital Power Peripherals Manual.

A schematic of the power stage of the PSFB is shown in Figure 7-2:

Figure 7-2 Schematic – PSFB Power Stage

Here is an overview of the key PSFB signals:

Figure 7-3 Key PSFB Signals

7.2.2.3 Fixed Signals to Bridge

The two top signals in the above drawing have fixed timing. The DPWM1CF and DPWM2CF signals are used for these pins. DPWMCxF refers to the signal coming out of the fault module of DPWMx, as shown in Figure 7-4.

Figure 7-4 Fixed Signals to Bridge

These signals are actually routed to pins DPWM3A and 3B using the Intra Mux with these statements:

Since these signals are really being used as events in the timer, the #defines are called EV5 and EV6. Here are the statements which initialize them:

Figure 7-5 Blank B Timing Information

The statements for DPWM1 are the same. Remember that DPWMC reuses the Blank B registers for timing information.

7.2.2.4 Dynamic Signals to Bridge

DPWM0 and 1 are set at normal mode. PCMC triggering signal (fault) chops DPWM0A and 1A cycle by cycle. The corresponding DPWM0B and 1B are used for synchronous rectifier MOSFET control. The same PCMC triggering signal is applied to DPWM2 and DPWM3. Both of these are set to normal mode as well. DPWM2 and 3 are chopped and their edges are used to generate the next two dynamic signals to the bridge. They are generated using the Edge Generator Module in DPWM2. The Edge Generator sources are DPWM2 and DPWM3. The edges used are:

Figure 7-6 Dynamic Signals to Bridge

The Edge Generator is configured with these statements:

The EDGE_EN bits are set for all 4 DPWMs. This is done to ensure that all signals have the same timing delay through the DPWM.

The final 6 gate signals are shown in Figure 7-7.

Figure 7-7 Final 6 Gate Signals

Note how the falling edge of DPWM2AF aligns with the X1 edge, and how the rising edge of DPWM2BF aligns with the X3 edge. The falling edges on DPWM2AF and DPWM3AF are caused by the peak detection logic. This is fed through the Cycle By Cycle logic. The Cycle By Cycle logic also has a special feature to control the rising edges of DPWM2BF (X1 and X3) and DPWM3BF (Y1 and Y3). It uses the value of Event3 – Event2 to control the time between the edges. The same feature is used with DPWM0 and DPWM1 to control the X2 and Y2 signals. Using the other 2 DPWMs permits these signals to have a different dead time.

The same setup can be used for voltage mode control. In this case, the Filter output sets the timing of the falling edge on DPWMxAF.

All DPWMs are configured in Normal mode, with CBC enabled. If external slope compensation is used, DPWM1A and DPWM1B are used to reset the external compensator at the beginning of each half cycle. If no PCMC event occurs, the values of Events 2 and 3 determine the locations of the edges, just as in open loop mode.

7.2.2.5 System Initialization for PCM

PCM (Peak Current Mode) is a specialized configuration for the UCD3138x which involves several peripherals. This section describes how it works across the peripherals.

7.2.2.5.2 Peak Current Detection

Peak current detection involves all the major modules of the DPPs, the Front End, Filter, Loop Mux, Fault Mux and the DPWMs. A drawing of the major elements is shown in Figure 7-8.

Figure 7-8 Peak Current Detection Function

All signals without arrows flow from left to right. The voltage loop is used to select a peak current level. This level is fed to the Ramp module to generate a compensation ramp. The compensation ramp is compared to the primary current by the PCMC comparator in the Front End. When the ramp value is greater than the primary current, the APCMC signal is sent to the DPWM, causing the events described in the previous sections.

The DPWM frame start and output pin signals can be used to trigger the Ramp Module. In this case, unlike in the case of other ramp module functions, each DPWM frame triggers the start of the ramp. The ramp steps every 32 ns.

The Filter is configured normally, there is no real difference for PCMC. The PCM_FILTER_SEL bits in the LoopMux.PCMCTRL register are used to select which filter is connected to the ramp module:

LoopMuxRegs.PCMCTRL.bit.PCM_FILTER_SEL =0; //select filter0

With Firmware Constant Power/Constant current, Filter 1 and Front End 1 are used as a current control loop, with the EADCDAC set to high current. If the voltage loop value becomes higher than the current loop value, then Filter 1 is used to control the PCM ramp start value:

LoopMuxRegs.PCMCTRL.bit.PCM_FILTER_SEL =1;
S P A C E //select filter1 for slope compensation source

In the ramp module, there are 2 bitfields in the RAMPCTRL register which must be configured. The PCM_START_SEL must be set to a 1 to enable the Filter to be used as a ramp start source. The RAMP_EN bit must be set, of course.

The DAC_STEP register sets the slope of the compensation ramp. The DAC value is in volts, of course, so it is necessary to calculate the slope after the current to voltage conversion. Here is the formula for converting from millivolts per microsecond to DACSTEP.

m = compensation slope in millivolts per microsecond

ACSTEP = 335.5 × M

In C, this can be written:

#define COMPENSATION_SLOPE 150 //compensation slope in millivolts per microsecond #define DACSTEP_COMP_VALUE ((int) (COMPENSATION_SLOPE*335.5) ) S P A C E //value in DACSTEP for desired compensation slope
S P A C E FeCtrl0Regs.DACSTEP.all = DACSTEP_COMP_VALUE;

It may also be necessary to set a ramp ending value in the RAMPDACEND register.

In addition, it is necessary to set the D2S_COMP_EN bit in the EADCCTRL register. This is for enabling the differential to single ended comparator function. The front end diagram leaves it out for simplicity, but the connection between the DAC and the EADC amplifier is actually differential. The PCMC comparator, however, is single ended. So a conversion is necessary as shown in Figure 7-9.

Figure 7-9 Differential to Single-Ended Comparator Function

The EADC_MODE bit in EADCCTRL should be set to a 5 for peak current mode.

The peak current detection signal next goes to the Loop Mux. The Fault Mux has only 1 APCM input, but there are 3 front ends. So the PCM_FE_SEL bits in APCMCTRL must be used to select which front end is used:

LoopMuxRegs.APCMCTRL.bit.PCM_FE_SEL = 2; // use FE2 for PCM */

The PCM_EN bit must also be set.

LoopMuxRegs.APCMCTRL.bit.PCM_EN = 1; // Enable PCM

Next the Fault Mux is used to enable the APCM bit to the CLIM/CBC signal to the DPWM. There are 4 DPWMxCLIM registers, one for each DPWM. The ANALOG_PCM_EN bit must be set in each one to connect the PCM detection signal to the CLIM/CBC signal on each DPWM. For the latest configuration information on all of these bits, consult the appropriate EVM firmware. To avoid errors, it is best to configure your hardware design using the same DPWMs, filters, and front ends for the same functions as the EVM.

DPWM timing is used to trigger the start of the ramp. This is selected by the FECTRLxMUX registers in the Loop Mux. DPWMx_FRAME_SYNC_EN bits, when set, cause the ramp to be triggered at the start of the DPWM period.

7.2.5.1 Device Grounding and Layout Guidelines

• Single ground is recommended: SGND. A multilayer such as 4 layers board is recommended so that one solid SGND is dedicated for return current path, referred to the layout example.
• Apply multiple different capacitors for different frequency range on decoupling circuits. Each capacitor has different ESL, and ESR, and they have different frequency response.
• Avoid long traces close to radiation components, and place them into an internal layer, and it is preferred to have grounding shield, and in the end, add a termination circuit.
• Analog circuit such as ADC sensing lines needs a return current path into the analog circuitry; digital circuit such as GPIO, PMBus and PWM has a return current path into the digital circuitry; although with a single plane, still try to avoid to mix analog current and digital current.
• Don’t use a ferrite bead or larger than 3-Ω resistor to connect between V33A and V33D.
• Both 3.3VD and 3.3VA should have local decoupling capacitors close to the device power pins, add vias to connect decoupling caps directly to SGND.
• Avoid negative current/negative voltage on all pins, so Schottky diodes may need to clamp the voltage; avoid the voltage spike on all pins more than 3.8 V or less than –0.3 V, add Schottky diodes on the pins which could have voltage spikes during surge test; be aware that a Schottky has relatively higher leakage current, which can affect the voltage sensing at high temperature.
• If V33 slew rate is less than 2.5 V/ms the RESET pin should have a 2.21-kΩ resistor between the reset pin and V33D and a 2.2-µF capacitor from RESET to ground. For more details please refer to the UCD3138 Family - Practical Design Guideline This capacitor must be located close to the device RESET pin.
• The 2.2-µF capacitor between V33D and BP18 can be removed due to internal enhancement design.
• Configure unused GPIO pins to be inputs or connect them to the ground (DGND or SGND); when an external pull-up resistor is used for GPIO, the pull-up resistor needs to be 1kOhm or higher.

7.2.5.2 Layout Example

Figure 7-13 PCB Layout Example