The ADS127L01 is a 24-bit, delta-sigma (ΔΣ), analog-to-digital converter (ADC) with data rates up to 512 kSPS. This device offers a unique combination of excellent dc accuracy and outstanding ac performance. The high-order, chopper-stabilized modulator achieves very low drift with low in-band noise. The integrated decimation filter suppresses modulator out-of-band noise. In addition to al low-latency filter, the ADS127L01 provides multiple Wideband filters with less than ±0.00004 dB of ripple, and an option for –116-dB stop-band attenuation at the Nyquist rate.
Traditionally, industrial delta-sigma ADCs that offer good drift performance use digital filters with large passband droop. As a result, industrial delta-sigma ADCs have limited signal bandwidth and are mostly suited for dc measurements. High-resolution ADCs in audio applications offer larger usable bandwidths, but the offset and drift specifications are significantly weaker than industrial counterparts. The ADS127L01 combines these converters, providing high-precision industrial measurement with excellent dc and ac specifications over an extended industrial temperature range of –40°C to +125°C.
A variety of operating modes allow for optimization of speed, resolution, and power. A programmable serial interface with one of three options (SPI, frame-sync slave, or frame-sync master) provides convenient interfacing across isolation barriers to microcontrollers or digital signal processors (DSPs).
PART NUMBER | PACKAGE | BODY SIZE (NOM) |
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ADS127L01 | TQFP (32) | 5.00 mm × 5.00 mm |
Changes from A Revision (May 2016) to B Revision
Changes from * Revision (April 2016) to A Revision
PIN | I/O | DESCRIPTION(3) | |||
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NO. | NAME | ||||
1 | LVDD | Supply | LVDD analog supply. INTLDO = 0: LVDD is an analog-supply output pin. Connect a 1-µF capacitor to AGND. INTLDO = 1: LVDD is an analog-supply input pin. Connect to a 1.8-V supply. |
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2 | CAP1 | Analog output | Modulator common-mode voltage. Connect a 1-µF capacitor to AGND |
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3 | AINN | Analog input | Negative analog input. | ||
4 | AINP | Analog input | Positive analog input. | ||
5 | AGND | Supply | Analog ground. | ||
6 | AVDD | Supply | Analog supply. Connect a 1-μF capacitor to AGND. |
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7 | REXT | Analog input | Analog power-scaling bias resistor pin. Recommended external resistor values: REXT = 60.4 kΩ to AGND for high-resolution (HR) and low-power (LP) modes REXT = 120 kΩ to AGND for very-low-power (VLP) mode |
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8 | INTLDO | Digital input | LVDD voltage selection pin (pull high to AVDD or low to AGND through 10-kΩ resistor). 0: Internal analog low-dropout regulator (LDO) for LVDD voltage supply. 1: External LVDD voltage supply. |
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9 | REFP | Analog input | Positive analog reference input. Connect a minimum 10-μF capacitor to REFN |
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10 | REFN | Analog input | Negative analog reference input. | ||
11 | CAP2 | Analog output | Reference common-mode voltage. Connect a 1-µF capacitor to AGND. |
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12 | FILTER1 | Digital input | Digital filter select pin(1). 00: Wideband 1 filter (WB1) 01: Wideband 2 filter (WB2) 10: Low-latency filter (LL) 11: Reserved |
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13 | FILTER0 | Digital input | |||
14 | FSMODE | Digital input | Frame-sync mode pin(1). 0: Slave mode 1: Master mode. Applies to Frame-Sync interface mode only. No effect in SPI interface mode. |
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15 | OSR1 | Digital input | Oversampling ratio (OSR) pin for the decimation filters(1). Wideband filters, FILTER[1:0] = 00 or 01: 00: 32x oversampling (OSR 32) 01: 64x oversampling (OSR 64) 10: 128x oversampling (OSR 128) 11: 256x oversampling (OSR 256) Low-latency filter, FILTER[1:0] = 10: 00: 32x oversampling (OSR 32) 01: 128x oversampling (OSR 128) 10: 512x oversampling (OSR 512) 11: 2048x oversampling (OSR 2048) |
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16 | OSR0 | Digital input | |||
17 | START | Digital input | Synchronization signal to start or restart a conversion. | ||
18 | DAISYIN | Digital input | Daisy-chain input. | ||
19 | DRDY/FSYNC | Digital input/output | SPI interface: Data ready, active low(2). Frame-sync interface: Frame-sync input signal(2) |
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20 | DOUT | Digital output | Serial data output | ||
21 | DIN | Digital input | Serial data input. Tie directly to DGND when using the frame-sync interface. |
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22 | SCLK | Digital input/output | Serial clock input(2). | ||
23 | CS | Digital input | Chip select. Tie directly to DGND when using the frame-sync interface. |
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24 | CLK | Digital input | Master clock input. | ||
25 | CAP3 | Analog output | Internally-generated digital operating voltage. Connect a 1-µF capacitor to DGND. |
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26 | DGND | Supply | Digital ground. | ||
27 | DVDD | Supply | Digital supply. Connect a 1-μF capacitor to DGND(2) |
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28 | RESET/PWDN | Digital input | Reset or power-down pin, active low(2). | ||
29 | HR | Digital input | ADC operating mode(1). 1: High-resolution (HR) 0: Low-power (LP) or very-low-power (VLP)(4) |
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30 | FORMAT | Digital input | Interface select pin(1). 0: SPI 1: Frame-Sync |
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31 | AGND | Supply | Analog ground. | ||
32 | AVDD | Supply | Analog supply. Decouple AVDD to AGND with a 1-μF capacitor. |
MIN | MAX | UNIT | ||
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Voltage | AVDD to AGND | –0.3 | 4.0 | V |
DVDD to DGND | –0.3 | 4.0 | ||
LVDD to AGND | –0.3 | 2.0 | ||
AGND to DGND | –0.3 | 0.3 | ||
REFP to AGND | –0.3 | AVDD + 0.3 | ||
REFN to AGND | –0.3 | AVDD + 0.3 | ||
Analog input | AGND – 0.3 | AVDD + 0.3 | ||
Digital input | DGND – 0.3 | DVDD + 0.3 | ||
Current | Input, continuous, any pin except power supply pins (2) | –10 | 10 | mA |
Temperature | Operating ambient, TA | –40 | 125 | °C |
Junction, TJ | 150 | |||
Storage, Tstg | –60 | 150 |
VALUE | UNIT | |||
---|---|---|---|---|
V(ESD) | Electrostatic discharge | Human-body model (HBM), per ANSI/ESDA/JEDEC JS-001(1) | ±2000 | V |
Charged-device model (CDM), per JEDEC specification JESD22-C101(2) | ±1000 |
MIN | NOM | MAX | UNIT | |||
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POWER SUPPLY | ||||||
AVDD | Analog power supply | 2.7 | 3.0 | 3.6 | V | |
LVDD | Low voltage analog supply | INTLDO = 1 | 1.7 | 1.8 | 1.9 | V |
DVDD | Digital supply | 1.7 | 1.8 | 3.6 | V | |
ANALOG INPUTS | ||||||
VIN | Differential input voltage | VIN = (VAINP – VAINN) | –VREF | VREF | V | |
VAINP, VAINN | Absolute input voltage | AINP or AINN to AGND | AGND | AVDD | V | |
VCM | Common-mode input voltage | VCM = (VAINP + VAINN) / 2 | AVDD / 2 | V | ||
VOLTAGE REFERENCE INPUTS | ||||||
VREFN | Negative reference input | AGND – 0.1 | AGND | AGND + 1.0 | V | |
VREFP | Positive reference input | VREFN + 0.5 | 2.5 | AVDD | V | |
VREF | Reference input voltage | VREF = VREFP – VREFN | 0.5 | 2.5 | 3.0 | V |
EXTERNAL CLOCK SOURCE | ||||||
fCLK | Master clock rate(1) | HR mode | 0.1 | 16.384 | 17.6 | MHz |
LP mode | 0.1 | 8.192 | 8.8 | |||
VLP mode | 0.1 | 4.096 | 4.4 | |||
DIGITAL INPUTS | ||||||
Input voltage | DGND | DVDD | V | |||
TEMPERATURE RANGE | ||||||
TA | Operating ambient temperature | –40 | 125 | °C |
THERMAL METRIC(1) | ADS127L01 | UNIT | |
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PBS (TQFP) | |||
32 PINS | |||
RθJA | Junction-to-ambient thermal resistance | 73.4 | °C/W |
RθJC(top) | Junction-to-case (top) thermal resistance | 15.9 | °C/W |
RθJB | Junction-to-board thermal resistance | 26.7 | °C/W |
ψJT | Junction-to-top characterization parameter | 0.4 | °C/W |
ψJB | Junction-to-board characterization parameter | 26.5 | °C/W |
RθJC(bot) | Junction-to-case (bottom) thermal resistance | N/A | °C/W |
PARAMETER | TEST CONDITIONS | MIN | TYP | MAX | UNIT | |||
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ANALOG INPUTS | ||||||||
Differential input impedance | HR mode, fCLK = 16.384 MHz | 5 | kΩ | |||||
LP mode, fCLK = 8.192 MHz | 11 | |||||||
VLP mode, fCLK = 4.096 MHz | 23 | |||||||
DC PERFORMANCE | ||||||||
Resolution | No missing codes | 24 | Bits | |||||
fDATA | Data rate | HR mode | Wideband filters | 512, 256, 128, 64 | kSPS | |||
Low-latency filter | 512, 128, 32, 8 | |||||||
LP mode | Wideband filters | 256, 128, 64, 32 | ||||||
Low-latency filter | 256, 64, 16, 4 | |||||||
VLP mode | Wideband filters | 128, 64, 32, 16 | ||||||
Low-latency filter | 128, 32, 8, 2 | |||||||
INL | Integral nonlinearity(1) | HR mode | VCM = AVDD / 2 | 2.5 | 10 | ppm | ||
LP mode | VCM = AVDD / 2 | 1 | 5 | |||||
VLP mode | VCM = AVDD / 2 | 1 | 5 | |||||
Offset error | ±0.1 | mV | ||||||
Offset drift | 1.5 | 3.0 | μV/°C | |||||
Gain error | 0.2 | %FSR | ||||||
Gain calibration accuracy | 0.003% | |||||||
Gain drift | HR mode | 0.8 | 3 | ppm/°C | ||||
LP mode | 0.4 | 2.5 | ||||||
VLP mode | 0.2 | 2 | ||||||
Noise(2) | HR mode | WB2, OSR 32 | 10.6 | μVRMS | ||||
WB2, OSR 64 | 7.3 | 10.1 | ||||||
WB2, OSR 128 | 5.1 | 7.2 | ||||||
WB2, OSR 256 | 3.6 | 5.2 | ||||||
CMRR | Common-mode rejection ratio | fCM = 60 Hz | 95 | dB | ||||
PSRR | Power-supply rejection ratio | fPS = 60 Hz | AVDD | 90 | dB | |||
DVDD | 85 | |||||||
LVDD | 80 | |||||||
AC PERFORMANCE | ||||||||
SNR | Signal-to-noise ratio(2)(3) | WB2, OSR 32 | 104.4 | dB | ||||
WB2, OSR 64 | 104.9 | 107.8 | ||||||
WB2, OSR 128 | 107.9 | 110.9 | ||||||
WB2, OSR 256 | 110.6 | 113.9 | ||||||
WB2, OSR 32, VREF = 3 V | 105.8 | |||||||
WB2, OSR 64, VREF = 3 V | 109.3 | |||||||
WB2, OSR 128, VREF = 3 V | 112 | |||||||
WB2, OSR 256, VREF = 3 V | 115.5 | |||||||
THD | Total harmonic distortion(4) | HR mode, fIN = 4 kHz, VIN = –0.5 dBFS | –113 | dB | ||||
LP mode, fIN = 4 kHz, VIN = –0.5 dBFS | –126 | |||||||
VLP mode, fIN = 4 kHz, VIN = –0.5 dBFS | –129 | |||||||
SFDR | Spurious-free dynamic range | HR mode | –115 | dB | ||||
LP mode | –130 | |||||||
VLP mode | –130 | |||||||
DIGITAL FILTER RESPONSE: WIDEBAND | ||||||||
Bandwidth | See Table 1 | |||||||
Pass-band ripple | ±0.000032 | dB | ||||||
Transition band | FILTER[1:0] = 00 (WB1) | (0.45 to 0.55) × fDATA | Hz | |||||
FILTER[1:0] = 01 (WB2) | (0.40 to 0.50) × fDATA | |||||||
Stop-band attenuation | 116 | dB | ||||||
Group delay | 42 / fDATA | s | ||||||
Settling time | Complete settling | 84 / fDATA | s | |||||
DIGITAL FILTER RESPONSE: LOW-LATENCY | ||||||||
Bandwidth | See Table 2 | |||||||
Group delay | See Low-Latency Filter section | |||||||
Settling time | See Low-Latency Filter section | |||||||
VOLTAGE REFERENCE INPUTS | ||||||||
Reference input impedance | HR mode | 2.2 | kΩ | |||||
LP mode | 3.2 | |||||||
VLP mode | 4 | |||||||
SYSTEM MONITORS | ||||||||
Input over-range detect accuracy | ±100 | mV | ||||||
DIGITAL INPUT/OUTPUT (DVDD = 1.7 V to 3.6 V) | ||||||||
VIH | High-level input voltage | 0.7 DVDD | DVDD | V | ||||
VIL | Low-level input voltage | DGND | 0.3 DVDD | V | ||||
VOH | High-level output voltage | IOH = 2 mA | 0.8 DVDD | DVDD | V | |||
VOL | Low-level output voltage | IOL = 2 mA | DGND | 0.2 DVDD | V | |||
IH | Input leakage, high | IH = 3.6 V | –10 | 10 | μA | |||
IL | Input leakage, low | IL = DGND | –10 | 10 | μA | |||
POWER SUPPLY | ||||||||
Power-down current | AVDD | INTLDO = 0 | 8 | μA | ||||
INTLDO = 1 | 2 | |||||||
DVDD | 0.6 | |||||||
LVDD, INTLDO = 1 | 0.6 | |||||||
IAVDD | AVDD current | HR mode | 1.3 | 1.6 | mA | |||
LP mode | 0.8 | 1.0 | ||||||
VLP mode | 0.4 | 0.6 | ||||||
ILVDD | LVDD current(5) (6) | HR mode | 9.3 | 11 | mA | |||
LP mode | 4.6 | 5.5 | ||||||
VLP mode | 2.3 | 2.8 | ||||||
IDVDD | DVDD current(2) | HR mode | OSR 128 | 2.8 | 3.4 | mA | ||
LP mode | OSR 128 | 1.5 | 1.8 | |||||
VLP mode | OSR 128 | 0.8 | 1.1 | |||||
PD | Power dissipation | HR mode, OSR 128, AVDD = 3.0 V, DVDD = 1.8 V |
INTLDO = 1, LVDD = 1.8 V, |
25.7 | 30.8 | mW | ||
INTLDO = 0 | 36.8 | 44.2 | ||||||
LP mode, OSR 128, AVDD = 3.0 V, DVDD = 1.8 V |
INTLDO = 1, LVDD = 1.8 V, |
13.4 | 16.1 | |||||
INTLDO = 0 | 18.9 | 22.7 | ||||||
VLP mode, OSR 128, AVDD = 3.0 V, DVDD = 1.8 V |
INTLDO = 1, LVDD = 1.8 V, |
6.8 | 8.2 | |||||
INTLDO = 0 | 9.5 | 11.4 |
2.8 V < DVDD ≤ 3.6 V | 1.7 V ≤ DVDD ≤ 2.8 V | UNIT | |||||||
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MIN | TYP | MAX | MIN | TYP | MAX | ||||
tc(CLK) | Master clock period | HR mode | 57 | 10,000 | 57 | 10,000 | ns | ||
LP mode | 114 | 10,000 | 114 | 10,000 | |||||
VLP mode | 227 | 10,000 | 227 | 10,000 | |||||
tw(CP) | Pulse duration, Master clock high or low | HR mode | 28 | 5,000 | 28 | 5,000 | ns | ||
LP mode | 56 | 5,000 | 56 | 5,000 | |||||
VLP mode | 112 | 5,000 | 112 | 5,000 | |||||
td(CSSC) | Delay time, CS falling edge to first SCLK rising edge(1) | 8 | 12 | ns | |||||
tc(SC) | SCLK period | 40 | 6250 | 50 | 6250 | ns | |||
tw(SCHL) | Pulse duration, SCLK high or low | 20 | 25 | ns | |||||
tsu(DI) | Setup time, DIN valid before SCLK falling edge | 6 | 9 | ns | |||||
th(DI) | Hold time, DIN valid after SCLK falling edge | 8 | 9 | ns | |||||
tw(CSH) | Pulse duration, CS high | 6 | 6 | tCLK | |||||
td(SCCS) | Delay time, final SCLK falling edge to CS rising edge | 2 | 2 | tCLK | |||||
td(DECODE) | Delay time, command decode time | 4 | 4 | tCLK | |||||
SPI timeout(2) | TOUT_DEL = 0 | 216 | 216 | tCLK | |||||
TOUT_DEL = 1 | 214 | 214 | tCLK | ||||||
tsu(DCI) | Setup time, DAISYIN valid before SCLK falling edge | 5 | 8 | ns | |||||
th(DCI) | Hold time, DAISYIN valid after SCLK falling edge | 20 | 25 | ns |
2.8 V < DVDD ≤ 3.6 V | 1.7 V ≤ DVDD ≤ 2.8 V | UNIT | |||||||
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MIN | TYP | MAX | MIN | TYP | MAX | ||||
tp(CSDO) | Propagation delay time, CS falling edge to DOUT driven |
12 | 18 | ns | |||||
tp(SCDO) | Propagation delay time, SCLK rising edge to valid new DOUT |
15 | 21 | ns | |||||
tv(DO) | Valid time, SCLK falling edge to DOUT invalid | 18 | tSCLK / 2 | 20 | tSCLK / 2 | ns | |||
tp(CSDOZ) | Propagation delay time, CS rising edge to DOUT high impedance |
20 | 20 | ns |
NOINDENT:
NOTE: SPI settings are CPOL = 0 and CPHA = 1.1.7 V ≤ DVDD ≤ 3.6 V | UNIT | |||||
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MIN | TYP | MAX | ||||
tc(CLK) | Master clock period | HR mode | 57 | 10,000 | ns | |
LP mode | 114 | 10,000 | ||||
VLP mode | 227 | 10,000 | ||||
tw(CP) | Pulse duration, Master clock high or low | HR mode | 28 | 5,000 | ns | |
LP mode | 56 | 5,000 | ||||
VLP mode | 112 | 5,000 |
2.8 V < DVDD ≤ 3.6 V | 1.7 V ≤ DVDD ≤ 2.8 V | UNIT | |||||||
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MIN | TYP | MAX | MIN | TYP | MAX | ||||
td(CSC) | Delay time, CLK rising edge to SCLK falling edge | 15 | 15 | ns | |||||
tc(FRAME) | Frame period | 1 / fDATA | 1 / fDATA | s | |||||
tw(FP) | Pulse duration, FSYNC high or low | 1 / (2fDATA) | 1 / (2fDATA) | s | |||||
td(FSSC) | Delay time, FSYNC rising edge to SCLK falling edge | 6 | 8 | ns | |||||
tc(SC) | SCLK period | 1 / (32fDATA) | 1 / (32fDATA) | s | |||||
tw(SCHL) | Pulse duration, SCLK high or low | 1 / (64fDATA) | 1 / (64fDATA) | s | |||||
tv(DO) | Valid time, SCLK rising edge to DOUT invalid | 25 | 25 | ns | |||||
tp(SCDO) | Propagation delay time, SCLK falling edge to DOUT driven |
15 | 17 | ns | |||||
tp(FSDO) | Propagation delay time, FSYNC rising edge to DOUT MSB valid |
12 | 15 | ns |
2.8 V < DVDD ≤ 3.6 V | 1.7 V ≤ DVDD ≤ 2.8 V | UNIT | |||||||
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MIN | TYP | MAX | MIN | TYP | MAX | ||||
tc(CLK) | Master clock period | HR mode | 57 | 10,000 | 57 | 10,000 | ns | ||
LP mode | 114 | 10,000 | 114 | 10,000 | |||||
VLP mode | 227 | 10,000 | 227 | 10,000 | |||||
tw(CP) | Pulse duration, Master clock high or low | HR mode | 28 | 5,000 | 28 | 5,000 | ns | ||
LP mode | 56 | 5,000 | 56 | 5,000 | |||||
VLP mode | 112 | 5,000 | 112 | 5,000 | |||||
td(CSC) | Delay time, CLK rising edge to SCLK falling edge | 2 | 2 | ns | |||||
tc(FRAME) | Frame period | 1 / fDATA | 1 / fDATA | s | |||||
tw(FP) | Pulse durration, FSYNC high or low | 2 | 2 | tSCLK | |||||
td(FSSC) | Delay time, FSYNC rising edge to SCLK falling edge | 6 | 6 | ns | |||||
td(SCFS) | Delay time, SCLK falling edge to FSYNC rising edge | 2 | 2 | ns | |||||
tc(SC) | SCLK period | 40 | 56 | ns | |||||
tw(SCHL) | Pulse duration, SCLK high or low | 20 | 28 | ns | |||||
DAISY-CHAIN TIMING | |||||||||
tsu(DCI) | Setup time, DAISYIN valid before SCLK rising edge | 8 | 8 | ns | |||||
th(DCI) | Hold time, DAISYIN valid after SCLK rising edge | 25 | 31 | ns |
2.8 V < DVDD ≤ 3.6 V | 1.7 V ≤ DVDD ≤ 2.8 V | UNIT | |||||||
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MIN | TYP | MAX | MIN | TYP | MAX | ||||
tv(DO) | Valid time, SCLK rising edge to DOUT invalid | 17 | 25 | ns | |||||
tp(SCDO) | Propagation delay time, SCLK falling edge to valid new DOUT |
22 | 22 | ns | |||||
tp(FSDO) | Propagation delay time, FSYNC rising edge to DOUT MSB valid |
15 | 22 | 25 | 32 | ns |
fIN = 4 kHz, VIN = –0.5 dBFS, HR mode, WB1, 512 kSPS, 32768 samples |
fIN = 4 kHz, VIN = –0.5 dBFS, LP mode, WB2, 256 kSPS, 32768 samples |
fIN = 4 kHz, VIN = –0.5 dBFS, VLP mode, WB2, 128 kSPS, 32768 samples |
Inputs shorted, HR mode, WB2, 512 kSPS, 32768 samples |
Inputs shorted, VLP mode, WB2, 128 kSPS, 32768 samples |
Inputs shorted, HR mode, 65536 points |
Inputs shorted |
WB2, OSR 32 |
HR mode, fIN = 4 kHz, VIN = –0.5 dBFS |
HR mode, fIN = 4 kHz, VIN = –0.5 dBFS |
VLP mode, fIN = 4 kHz, VIN = –0.5 dBFS |
HR mode, 30 Devices |
VLP mode, 30 Devices |
Inputs shorted, HR mode |
HR mode, INTLDO = 1 |
INTLDO = 1, LVDD = 1.8 V |
Inputs shorted, HR mode, LL, 512 kSPS, 32768 samples |
Inputs shorted, HR mode, LL, 32 kSPS, 32768 samples |
Inputs shorted, HR mode, LL, 512 kSPS, 32768 samples |
Inputs shorted, HR mode, LL, 32 kSPS, 32768 samples |
fIN = 4 kHz, VIN = –20 dBFS, HR mode, WB2, 512 kSPS, 32768 samples |
fIN = 4 kHz, VIN = –20 dBFS, HR mode, WB1, 512 kSPS, 32768 samples |
fIN = 4 kHz, VIN = –20 dBFS, LP mode, WB2, 256 kSPS, 32768 samples |
fIN = 4 kHz, VIN = –20 dBFS, VLP mode, WB2, 128 kSPS, 32768 samples |
Inputs shorted, LP mode, WB2, 256 kSPS, 32768 samples |
HR mode, 0.5 seconds data collection space |
Inputs shorted, HR mode |
Inputs shorted, HR mode |
WB2, OSR 32 |
fIN = 4 kHz, HR mode |
LP mode, fIN = 4 kHz, VIN = –0.5 dBFS |
Inputs shorted |
Inputs shorted |
Inputs shorted, 30 devices |
LP mode, 30 Devices |
HR mode |
HR mode, fCLK = 16.384 MHz |
HR mode, INTLDO = 0 |
INTLDO = 0 |
Inputs shorted, HR mode, LL, 128 kSPS, 32768 samples |
Inputs shorted, HR mode, LL, 8 kSPS, 32768 samples |
Inputs shorted, HR mode, LL, 128 kSPS, 32768 samples |
Inputs shorted, HR mode, LL, 8 kSPS, 32768 samples |
Adjust the oversampling ratio (OSR) to control the data rate and change the digital filter in order to optimize the noise performance of the ADS127L01. Hardware control pins offer four oversampling options and three selectable digital filter options to configure the ADC for a specific bandwidth of interest. When averaging is increased by reducing the data rate (increasing the OSR), the in-band noise drops as more samples from the modulator are averaged to yield one conversion result. Table 1 and Table 2 summarize the device noise performance across the various oversampling and digital filter options. Wideband 1 filter has a filter transition band of (0.45 to 0.55) fDATA, and Wideband 2 filter has a filter transition band of (0.40 to 0.50) fDATA. Data are representative of typical noise performance at TA = 25°C with an external 2.5-V reference. Data shown are the result of one standard deviation of the readings with the inputs shorted together and biased to midsupply. A minimum of 1,000 consecutive readings are used to calculate the VRMS_noise voltage noise for each measurement. Equation 1 is used to convert the noise in VRMS_noise to SNR, and Equation 2 is used to convert the noise in VRMS_noise to ENOB. The peak-to-peak noise for the Low-latency filter is defined as VPP_noise.
The ADS127L01 is a 24-bit delta-sigma (ΔΣ) ADC that offers a combination of excellent dc accuracy and ac performance. The flexible digital-filter options make it suitable for both dc and ac applications. The device is hardware programmable, making it easy to configure for a variety of applications without the need to program any registers.
The Functional Block Diagram shows the main internal features of the ADS127L01. The converter is comprised of a third-order, chopper-stabilized, delta-sigma modulator, that measures the differential input signal, VIN = (VAINP – VAINN), against the differential reference, VREF = (VREFP – VREFN). The converter core consists of a differential, switched-capacitor, delta-sigma modulator followed by a selectable digital filter. The digital-filter low-latency path uses a cascaded combination of a fifth-order sinc and a first-order sinc filter, ideal for applications requiring fast response time or systems using a multiplexed input. Two wide-bandwidth paths (Wideband 1 and Wideband 2) are also available, providing outstanding frequency response with very low pass-band ripple, a steep-transition band, and high stop-band attenuation. The ADS127L01 provides two selectable options for transition-band frequency. The Wideband-filter paths are suited for applications that require high-resolution measurements of high-frequency, ac-signal content. To allow tradeoffs among speed, resolution, and power, three operating modes are supported: high-resolution (HR), low-power (LP), and very-low-power (VLP).
In HR mode, SNR = 104.4 dB (VREF = 2.5 V) at a maximum data rate of 512 kSPS. At this data rate, the power dissipation is only 35 mW, and scales with master clock frequency. In LP mode, the maximum data rate is 256 kSPS, while consuming only 19 mW of power. In VLP mode, the maximum data rate is 128 kSPS, while consuming only 9 mW of power.
Configure the ADS127L01 by setting the appropriate hardware I/O pins. Registers are available for gain and offset calibrations. Three interface communication modes are available, providing flexibility for convenient interfacing to microcontrollers, DSPs, or FPGAs. SPI, frame-sync slave, or frame-sync master communication modes are hardware selectable on the device. The ADS127L01 has a daisy-chain output available, and can synchronize externally to another device or system using the START signal. The daisy-chain configuration allows the device to be used conveniently in systems that require multiple channels.
This section discusses the details of the ADS127L01 internal functional elements. Throughout this document, fCLK denotes the frequency of the signal at the CLK pin, tCLK denotes the period of the signal at the CLK pin, fDATA denotes the output data rate, and tDATA denotes the time period of the output data.
The ADS127L01 measures the differential input signal VIN = (VAINP – VAINN) against the differential reference VREF = (VREFP – VREFN). The most positive measurable differential input is +VREF and the most negative measurable differential input is –VREF.
For optimum performance, drive the ADS127L01 inputs differentially, centered around a common-mode voltage of AVDD / 2. Alternatively, if the signal is of pseudo-differential nature, the negative input can be held at a constant voltage other than 0 V (typically AVDD / 2), and the voltage on the positive input can change. Figure 58 and Figure 59 show examples of both fully-differential and pseudo-differential signals, respectively.
Electrostatic discharge (ESD) diodes to AVDD and AGND protect the inputs. To prevent the ESD diodes from turning on, the absolute voltage on any input must stay within the range provided by Equation 3:
The analog input pins, AINP and AINN, at the front end of the converter are connected directly to the switched-capacitor sampling network to measure the input voltage. Figure 60 shows a conceptual diagram of the modulator circuit charging and discharging the sampling capacitor through switches, although the actual implementation is slightly different. The sampling time (tCLK / 2) is equivalent to half the master clock period, and is the inverse of the modulator sampling frequency.
The average load presented by the switched-capacitor input can be modeled with an effective differential impedance, as shown in Figure 61. The effective impedance is a function of the modulator clock, and is equal to the master clock, fCLK. The ADS127L01 samples the input at very high speeds, and does not include an integrated buffer; a suitable driver must be used. See the Application and Implementation section for recommended driver circuit designs.
The ADC sampling network is connected to a delta-sigma modulator used to convert the analog input voltage into a data bit stream. The modulator is third-order, with a multibit quantizer that runs at the modulator clock frequency, fMOD, equal to the master clock frequency, fCLK.
The ADS127L01 offers three selectable digital filters to perform both filtering and decimation of the digital data stream coming from the modulator. The oversampling ratio (OSR) and digital-filter selection sets the overall frequency response for the data converter. The available filter options for the ADS127L01 are:
Use the hardware FILTER[1:0] pins shown in Table 11. Each filter has four OSR options (the ratio of the modulator sampling to the output data rate, or fMOD / fDATA), shown in Table 12, that are selectable through hardware OSR[1:0] pins. The low-latency sinc filter is a cascaded sinc5 and sinc1 filter, and provides OSR options to achieve data rates ranging from 8 kSPS to 512 kSPS when operating from a 16.384-MHz master clock. The two Wideband filters use a multistage FIR topology to provide linear phase response with very low pass-band ripple and high stop-band attenuation. Wideband filters 1 and 2 provide four OSRs to achieve data rates ranging from 64 kSPS to 512 kSPS when operating from a 16.384-MHz master clock.
Select the filter and data rate when START is low, or take the START or RESET/PWDN pin low and back high after a filter-path or data-rate change. If software commands are used to control conversions, use the STOP and START commands after a change to the filter path selection or the data rate. If a conversion is in process during a filter-path or data-rate change, the output data are not valid and must be discarded.
The low-latency sinc filter consists of two stages: a fixed-decimation, sinc5 filter, followed by a variable-decimation, sinc1 filter. The first-stage, sinc5 digital filter decimates by a fixed value of 32. When using OSR 32, the first-stage digital filter bypasses the second filter stage, and has a sinc5 frequency response profile. The second digital-filter stage provides an additional decimation of 4, 16, or 64 to create overall decimation options of 128, 512, and 2048. Together, the two stages create four selectable, Low-latency, filter data rates when operated from a 16.384-MHz clock: 512 kSPS, 128 kSPS, 32 kSPS, and 4 kSPS.
The low-pass filtering effect of the sinc filter sets the overall frequency response of the ADC when in low-latency filter mode. The frequency response of OSR 32 is from only the sinc5 filter stage. The frequency response of OSR 128, 512, or 2048 is the product of the sinc5 first-stage and sinc1 second-stage frequency responses. The overall filter response is given in Equation 4:
where
The inherent nature of the sinc filter response begins to attenuate frequencies as the signal moves away from dc. The pass band droop for inband ac signals makes the low-latency filter less ideal for ac signals.
As shown in Figure 62 and Figure 63, when OSR is set to 32, the digital filter frequency response follows a sinc5 transfer function with nulls occurring at fDATA and at multiples thereof. At the null frequencies, the filter has zero gain. Convert the x-axis from the data rate, fDATA, to terms of the master clock, fCLK, by using Equation 5:
Adjust the digital-filter response by changing the OSR or the master clock, fCLK. Noise tradeoffs are made with signal bandwidth and filter latency.
Selecting an OSR other than 32 superimposes new nulls from the second-stage sinc1 filter over the nulls produced by the sinc5 stage. The end result is a combined frequency response from a sinc5 function at OSR 32 with nulls created from the sinc1 second stage at fDATA and multiple thereof.
Figure 64 and Figure 65 illustrate the normalized frequency response of the Low-latency filter across all four OSR settings. OSR 32 follows a sinc5 frequency response, as highlighted in Figure 62. OSR 128, OSR 512, and OSR 2048 show a combined sinc5 and sinc1 response.
Figure 66, Figure 67, and Figure 68 illustrate the frequency response of OSR 128, OSR 512, and OSR 2048, respectively.
The Low-latency filter uses a multiple-stage, linear-phase, digital filter. Linear-phase filters exhibit constant delay time versus input frequency (also known as constant group delay). This feature of linear phase filters means that the time delay from any instant of the input signal to the corresponding same instant of the output data is constant and independent of the input-signal frequency. This behavior results in essentially zero phase error when measuring multitone signals.
The Low-latency filter takes several conversion cycles to provide fully-settled data following a START pin low-to-high transition or a START command. The OSR setting determines the exact number of conversion cycles for first new available data, as shown in Table 3. In SPI mode, the DRDY signal remains high until settled data are available. After settled data are available, a high-to-low transition on DRDY takes place. In frame-sync mode, DOUT shifts zeroes until settled data are available. Figure 69 shows the relationship between START to the first settled available data for SPI and frame-sync interface mode. See the Start Pin (START) section for exact timing for the START pin to first available data.
When applying an asynchronous step input to a converting ADS127L01, the output shift register does not gate data during digital-filter settling. The step-input-setting timing diagram shown in Figure 70 illustrates the converter step response with an asynchronous step input. The time that the analog input must be stable varies depending on the OSR. Table 3 summarizes the settling time of the Low-latency filter when a step input is applied to the input.
OSR | SETTLING TIME FROM START (tCLK Periods) |
INPUT SETTLING (DRDY or FSYNC Pulses) |
---|---|---|
32 | 160 | 5 |
128 | 288 | 3 |
512 | 672 | 2 |
2048 | 2208 | 2 |
The two Wideband filters use a multistage FIR topology to provide linear phase response with minimal pass-band ripple and high stop-band attenuation. The filters are well suited for measuring high-frequency ac signals while still maintaining excellent dc accuracy. Both Wideband filter options offer the same four OSR options; 32, 64, 128, and 256. The difference is in the transition band. When these four OSRs are paired with a 16.384-MHz clock, four selectable Wideband filter data rates are created: 512 kSPS, 256 kSPS, 128 kSPS, and 64 kSPS.
Figure 71 shows the frequency response of the Wideband 1 filter with a transition band of (0.45 to 0.55) × fDATA normalized to the output data rate, fDATA. Figure 72 shows the frequency response of the Wideband 2 filter with a transition band of (0.40 to 0.50) × fDATA normalized to the output data rate, fDATA. These plots are valid for all of the data rates available on the ADS127L01. Substitute the selected data rate, fDATA (calculated using Equation 5), to express the x-axis in absolute frequency. Figure 73 overlaps the transition band of the Wideband 1 and Wideband 2 filters, showing the difference in frequency response. The Wideband 2 filter frequency response is designed to attenuate out-of-band signals more than –116 dB by the Nyquist frequency (0.5 × fDATA) to reduce the effects of aliasing near the transition band.
FILTER[1:0] = 00 |
FILTER[1:0] = 01 |
The pass-band ripple for the two digital filters are shown in Figure 74 and Figure 75.
FILTER[1:0] = 00 |
FILTER[1:0] = 01 |
The overall frequency response repeats at the modulator sampling rate, which is the same as the input clock frequency, fCLK. Figure 76 shows the response with the fastest data rate selected (512 kSPS when fCLK = 16.384 MHz).
The Wideband filters use a multiple-stage, linear-phase, digital-filter architecture. Linear-phase filters exhibit constant delay time versus input frequency (also known as constant group delay). This feature of linear phase filters means that the time delay from any instant of the input signal to the corresponding same instant of the output data is constant and independent of the input-signal frequency. This behavior results in essentially zero phase error when measuring multitone signals.
The Wideband filters fully settle before outputting data after the START pin low-to-high transition or a START command is issued. The settling time of the Wideband filters is 84 conversion cycles; the DRDY signal idles high and does not assert until new settled data are available in SPI interface mode. In frame-sync interface mode, the output shift register outputs zeroes in place of the conversion data for 84 conversion cycles until the first settled data are available. A step input on the analog input requires multiple conversions to settle if START is not pulsed, or if the START command is not issued. Figure 77 shows the settling response with the x-axis normalized to conversions or DRDY/FSYNC cycles.
Figure 78 and Figure 79 plot the undershoot and overshoot from the Wideband digital filter during an input step function.
The ADC requires the connection of an external reference voltage for operation. The voltage reference for the device is the differential voltage between REFP and REFN: VREF = (VREFP – VREFN). The reference inputs are not buffered and use a sampling structure similar to that of the analog inputs, with the equivalent circuitry on the reference inputs shown in Figure 80. The load across REFP and REFN is presented by the switched-capacitor in parallel with a 6.4-kΩ resistor, and is modeled with an effective impedance (Zeff) proportional to the master clock, fCLK, as shown in Figure 81.
ESD diodes protect the reference inputs. To keep these diodes from turning on, make sure the voltages on the reference pins do not go below AGND by more than 0.3 V, and do not exceed AVDD by 0.3 V. Use external Schottky clamp diodes or series resistors to limit the input current to safe values if the reference input may exceed the absolute maximum ratings (see the Absolute Maximum Ratings table).
A high-quality reference voltage with the appropriate drive strength is required for achieving the best performance from the ADS127L01. Noise and drift on the reference degrade overall system performance. Use a minimum parallel combination of 10-µF and 0.1-µF ceramic bypass capacitors directly across the reference inputs, REFP and REFN. Place these capacitors as close as possible to the device on the layout. See the Application Information section for example reference circuits.
The ADS127L01 requires an external clock for operation. This clock signal is used for the sampling network of the modulator without any prescalers or dividers, and for the timing for the digital filter. Drive the ADC with an external clock by applying the clock input to the CLK pin. At the maximum data rate, the clock input is 16.384 MHz for HR mode, 8.192 MHz for LP mode, and 4.096 MHz for VLP mode.
A high-quality, low-jitter clock is essential for optimum performance measuring the high-frequency input signals. Any uncertainty during sampling of the input from clock jitter limits the maximum achievable SNR. For example, uses an external clock with better than 10 psrms jitter for a 200-kHz fIN. For a lower fIN, the target jitter requirement can be relaxed by –20 dB per decade. At fIN = 20 kHz, use a clock with better than 100-psrms jitter.
The selection of the external clock frequency (fCLK) does not affect the resolution of the ADS127L01. The output data rates scale with fCLK frequency down to a minimum clock frequency of fCLK = 100 kHz. Use a slower fCLK to reduce the ADC power consumption and relax the requirements of an external ADC drive circuit on the analog input and reference input.
Crystal clock oscillators are the recommended clock source. Make sure to avoid excess ringing on the clock input. A series resistor placed at the external clock buffer output often helps to reduce overshoot.
An out-of-range-detect system-monitor bit (INP) is available in the status word (see the Status Word section). The out-of-range detect bit flags (INP = 1) when the input exceeds the positive or negative full-scale range, set by VREF, with each conversion result. The input is monitored using an analog comparator. The flag is issued when the full-scale range is exceeded without waiting for the conversions to propagate through the digital filter. The INP bit is used for narrow out-of-range input glitches that may or may not be removed by the ADC digital filter.
The ADC incorporates optional offset- and gain-calibration registers to system-calibrate the ADC and signal chain when in SPI interface mode. Enable the offset calibration register by setting FSC bit (bit 5 in the Configuration register) to 1, and enable the gain calibration register by setting OFC bit (bit 4 in the Configuration register) to 1. The programmable offset calibration value is 24 bits wide, and the gain calibration value is 16 bits wide. Use calibration to correct internal ADC errors or overall system errors. Calibration is only supported through direct user calibration, requiring the user to calculate and write the correction values to the calibration registers. Perform a system offset calibration before full-scale calibration. After power-up, but before calibrating, wait for the power supplies and reference voltage to fully settle.
As shown in Figure 82, the value of the offset calibration register is subtracted from the filter output, and then multiplied by the full-scale register value. The data are then clipped to a 24-bit value to provide the final output.
Equation 6 shows the internal calibration on the data result.
The ADC offset calibration word is 24 bits, consisting of three 8-bit registers (OFC2, OFC, 1 OFC0), as shown in Table 4. The offset value is twos complement format with a maximum positive value equal to 7FFFFFh (for negative offset), and a maximum negative value equal to 800000h (for positive offset). A register value equal to 000000h has no offset correction. For offset calibration, short the ADC inputs or system inputs, and average the conversions; averaging reduces noise for a more accurate calibration. Write the average value to the offset calibration registers. The ADC subtracts the value from the conversion result.
REGISTER | BYTE ORDER | ADDRESS | BIT ORDER | |||||||
---|---|---|---|---|---|---|---|---|---|---|
OFC0 | LSB | 02h | OFC_B7 | OFC_B6 | OFC_B5 | OFC_B4 | OFC_B3 | OFC_B2 | OFC_B1 | OFC_B0 (LSB) |
OFC1 | MID | 03h | OFC_B15 | OFC_B14 | OFC_B13 | OFC_B12 | OFC_B11 | OFC_B10 | OFC_B9 | OFC_B8 |
OFC2 | MSB | 04h | OFC_B23 (MSB) | OFC_B22 | OFC_B21 | OFC_B20 | OFC_B19 | OFC_B18 | OFC_B17 | OFC_B16 |
The ADC gain calibration word is 16 bits consisting of two 8-bit registers (FSC1, FSC0), as shown in Table 5. The full-scale calibration value is twos compliment, with a unity-gain correction factor at a register value equal to 8000h. Table 6 shows register values for selected gain factors.
REGISTER | BYTE ORDER | ADDRESS | BIT ORDER | |||||||
---|---|---|---|---|---|---|---|---|---|---|
FSC0 | LSB | 05h | FSC_B7 | FSC_B6 | FSC_B5 | FSC_B4 | FSC_B3 | FSC_B2 | FSC_B1 | FSC_B0 (LSB) |
FSC1 | MSB | 06h | FSC_B15 (MSB) | FSC_B14 | FSC_B13 | FSC_B12 | FSC_B11 | FSC_B10 | FSC_B9 | FSC_B8 |
FSCAL[2:0] REGISTER VALUE | GAIN FACTOR |
---|---|
7FFFh | 2.00 |
8000h | 1.00 |
0000h | 0.00 |
For gain calibration, apply a dc calibration voltage that is less than positive full-scale voltage in order to avoid clipped codes (VIN < +FSR), and average the conversions to reduce noise for a more accurate calibration. Gain calibration is computed as shown in Equation 7, after offset error is removed.
If the actual code is higher than the expected value, then the calculated calibration value is less than 8000h, and the ADC gain is subsequently reduced. Write the calibration value to the gain calibration registers.
The ADS127L01 offers three operational modes: high-resolution (HR), low-power (LP), and very-low-power (VLP). These modes optimize power consumption by restricting the maximum master-clock frequency (fCLK) controlling the data rate. The status of the HR pin determines if the device is in HR mode or LP mode. Enter VLP mode by setting the ADS127L01 in LP mode, and increasing the value of the external REXT power scaling resistor from 60.4 kΩ to 120 kΩ. The tolerance on the REXT power-scaling resistor must be 1% or better. The analog current consumed by AVDD and LVDD decreases when in LP mode, and decreases further in VLP mode, with a tighter restriction on maximum master-clock frequency. Table 7 details the HR pin and REXT settings for each operating mode in the ADS127L01.
OPERATING MODE | OPERATING MODE SELECTION PIN (HR) | REXT VALUE | MAXIMUM fCLK |
---|---|---|---|
High-Resolution (HR) | 1 | 60.4 kΩ | 17.6 MHz |
Low-Power (LP) | 0 | 60.4 kΩ | 8.8 MHz |
Very-Low-Power (VLP) | 0 | 120 kΩ | 4.4 MHz |
The ADS127L01 uses two-state hardware mode pins for ADC configuration. The operating mode, interface selection, digital filter selection, and oversampling ratio (OSR) are all controlled through hardware pins. These pins are constantly monitored, and set by either pulling them high to DVDD, or low to DGND. Use pull-up or pull-down 100-kΩ resistors, or directly tie the pins to microcontroller or DSP I/O lines to set the state of the pins. When a change is sensed on the hardware mode pins after power-up, the ADC automatically issues a reset. To ensure synchronization, issue a software reset command, or pulse the RESET/PWDN pin following the mode change delay, td(MD).
When using the SPI interface mode, DRDY is held high after a mode change occurs until settled data are ready; see Figure 83 and Table 8.
SYMBOL | DESCRIPTION | MIN | TYP | MAX | UNIT | |
---|---|---|---|---|---|---|
td(MD) | Delay time, MODE pin rising edge to mode change | 3 | tCLK | |||
td(FILT) | Delay time, mode change to first modulator sample | 3.5 | 4.5 | tCLK | ||
td(NDR) | Delay time for new data to be ready | Wideband filters | 84 | tDATA | ||
Low-latency filter | See Table 3 | tDATA |
In Frame-sync intreface mode, the DOUT pins are held low after a mode change occurs until settled data are ready; see Figure 84 and Table 9. Data can be read from the device to detect when DOUT changes, indicating that data are valid.
SYMBOL | DESCRIPTION | MIN | TYP | MAX | UNIT | |
---|---|---|---|---|---|---|
td(MD) | Delay time, MODE pin rising edge to mode change | 3 | tCLK | |||
tsu(FILT) | Setup time, mode change to FSYNC rising edge | Frame-sync slave | 5 | tCLK | ||
Frame-sync master | 1 | tCLK | ||||
td(NDR) | Delay time for new data to be ready | Wideband filters | 84 | tDATA | ||
Low-latency filter | See Table 3 | tDATA |
Data are read from the ADS127L01 using one of two selectable interface modes, SPI or frame-sync. Use the FORMAT input pin to select among the two interface options.
If the frame-sync interface is selected, the ADS127L01 offers either a master or slave option, selectable using the FSMODE pin. Table 10 lists the available options.
FORMAT | FSMODE | INTERFACE MODE |
---|---|---|
0 | 0 | SPI |
0 | 1 | SPI |
1 | 0 | Frame-sync slave mode |
1 | 1 | Frame-sync master mode |
Three digital filter options are available in the ADS127L01: two Wideband filter options, and a Low-latency filter. See the Digital Filter section for detailed information on the digital filters and the frequency responses. The FILTER[1:0] hardware mode pins set the filter path selection for the modulator data, as shown in Table 11. Select the filter when START is low, or take the START or RESET/PWDN pin low and back high after a filter path change. If software commands are used to control conversions, use the STOP and START commands after a change to the filter path selection. If a conversion is in process during a filter path change, the output data are not valid and must be discarded.
FILTER1 | FILTER0 | SELECTED FILTER PATH | FILTER TRANSITION BAND |
---|---|---|---|
0 | 0 | Wideband 1 filter | 0.45 × fDATA to 0.55 × fDATA |
0 | 1 | Wideband 2 filter | 0.40 × fDATA to 0.50 × fDATA |
1 | 0 | Low-latency filter | SINC5 / SINC |
1 | 1 | Reserved: do not use |
The ADS127L01 has two hardware oversampling ratio (OSR) pins used to configure the converter data rate. The rate at which the modulator bit stream data is decimated differs depending on whether the Wideband or the Low-latency digital filter is used (set using the Digital-Filter Path Selection Pins (FILTER[1:0])). The OSR options and corresponding maximum data rate at fCLK = 16.384 MHz are shown in Table 12 for both the Wideband and the Low-latency filters. Change the OSR when START is low, or take the START or RESET/PWDN pin low and back high after changing the OSR. If software commands are used to control conversions, use the STOP and START commands after changing the OSR.
FILTER | OSR1 | OSR0 | OSR | DATA RATE (kSPS) AT fCLK = 16.384 MHz |
---|---|---|---|---|
Wideband filters | 0 | 0 | 32 | 512 |
0 | 1 | 64 | 256 | |
1 | 0 | 128 | 128 | |
1 | 1 | 256 | 64 | |
Low-latency filter | 0 | 0 | 32 | 512 |
0 | 1 | 128 | 128 | |
1 | 0 | 512 | 32 | |
1 | 1 | 2048 | 8 |
The START pin controls the start and stop of ADC conversions used for converter synchronization. Take the START pin low to stop conversions and reset the digital filter. Pull START high to start or restart the conversions.
Synchronization allows the conversion to be aligned with an external event, such as the changing of an external multiplexer on the analog inputs. The START pin is also used to synchronize multiple devices to within the same CLK cycle.
Figure 85 and Figure 86 illustrate the timing requirement for the START pin with respect to CLK in SPI and frame-sync interface modes. After synchronization, indication of valid data depends on whether SPI or frame-sync interface mode is used.
In the SPI interface mode, DRDY goes high as soon as START is taken low, as shown in Figure 85. After START is returned high, DRDY stays high while the digital filter completes reset and settles. After valid data are ready for retrieval, DRDY goes low.
SYMBOL | DESCRIPTION | MIN | TYP | MAX | UNIT | |
---|---|---|---|---|---|---|
tw(STL) | Pulse duration, START low | 4 | tCLK | |||
tsu(ST) | Setup time, START rising edge to CLK rising edge | 10 | ns | |||
td(FILT) | Delay time, START rising edge to first modulator sample | 4 | 5 | tCLK | ||
td(NDR) | Delay time for new data to be ready | Wideband filters | 84 | tDATA | ||
Low-latency filter | See Table 3 | tDATA |
In frame-sync interface, DOUT goes low as soon as START is taken low, as shown in Figure 86. After START is returned high, the following FSYNC rising edge releases the digital filter from reset to begin conversions. DOUT stays low while the digital filter is settling. Data are ready for retrieval on DOUT after the digital filter settles. For proper synchronization, FSYNC, SCLK, and CLK must be established before taking START high, and must then remain running. If either CLK, FSYNC or SCLK are interrupted or reset, reassert the START pin.
SYMBOL | DESCRIPTION | MIN | TYP | MAX | UNIT | |
---|---|---|---|---|---|---|
tw(STL) | Pulse duration, START low | 4 | tCLK | |||
tsu(ST) | Setup time, START rising edge to FSYNC rising edge | Frame-sync slave | 6 | tCLK | ||
Frame-sync master | 5 | tCLK | ||||
td(NDR) | Delay time for new data to be ready | Wideband filters | 84 | tDATA | ||
Low-latency filter | See Table 3 | tDATA |
In addition to the START pin, START and STOP commands are also available to control the start and stop of conversions, but only when using the SPI interface. Using the commands requires that the hardware START pin is tied low the entire time. The START command is also used to synchronize multiple ADS127L01s sharing the same SPI interface. See the SPI Commands section for information on using the START and STOP commands to control ADC conversions.
The RESET/PWDN pin has two functions, depending on the amount of time the pin is held in a low state. If RESET/PWDN is low for < 215 – 1 CLK periods, the ADS127L01 resets both the digital filter and register contents to default settings. The low-to-high transition of the RESET/PWDN pin brings the ADS127L01 out of reset by completing the digital filter reset, as shown in Figure 87 and Figure 88.
SYMBOL | DESCRIPTION | MIN | TYP | MAX | UNIT | |
---|---|---|---|---|---|---|
tw(RSL) | Pulse duration RESET/PWDN low | 4 | 215 – 1 | tCLK | ||
tsu(RS) | Setup time, RESET/PWDN rising edge to CLK rising edge | 10 | ns | |||
td(FILT) | Delay time, RESET/PWDN rising edge to first modulator sample | 37 | tCLK | |||
td(NDR) | Delay time for new data to be ready | Wideband filters | 84 | tDATA | ||
Low-latency filter | See Table 3 | tDATA |
SYMBOL | DESCRIPTION | MIN | TYP | MAX | UNIT | |
---|---|---|---|---|---|---|
tw(RSL) | Pulse duration RESET/PWDN low | 4 | 215 – 1 | tCLK | ||
tsu(RSS) | Frame-Sync Slave Mode: Setup time, RESET/PWDN rising edge to first FSYNC | 7 | tCLK | |||
tsu(RSM) | Frame-Sync Master Mode: Setup time, RESET/PWDN rising edge to CLK rising edge | 10 | ns | |||
td(RSM) | Frame-Sync Master Mode: Delay time, CLK rising edge to FSYNC rising edge | 4 | tCLK | |||
td(NDR) | Delay time for new data to be ready | Wideband filters | 84 | tDATA | ||
Low-latency filter | See Table 3 | tDATA |
If RESET/PWDN is low for > 215 – 1 CLK periods, the ADS127L01 enters power-down mode where both the analog and digital circuitry is completely deactivated. The digital inputs are internally disabled so there is no concern in driving the pins.
Use individual 1-MΩ pull-down resistors placed on CAP3 to DGND, SCLK to DGND, and DRDY/FSYNC to DGND if power-down mode is planned to be used. These resistors help discharge voltage when the device is placed in power-down mode. Shut down the CLK and SCLK in power-down mode to avoid additional power consumption.
Return the RESET/PWDN pin high to exit power-down mode. As shown in Figure 89 and Figure 90, a minimum of 215 + 37 master clock periods must elapse before the device exits power-down mode and begins sampling when using SPI interface mode. DRDY stays high after exiting power-down mode while the digital filter settles.
SYMBOL | DESCRIPTION | MIN | TYP | MAX | UNIT | |
---|---|---|---|---|---|---|
tw(PWDN) | Pulse duartionRESET/PWDN low | 215 | tCLK | |||
tsu(PWDN) | Setup time, RESET/PWDN rising edge to CLK rising edge | 10 | ns | |||
td(POR) | Delay time, power-on-reset complete following RESET/PWDN rising edge | 215 + 37 | tCLK | |||
td(NDR) | Delay time for new data to be ready | Wideband filters | 84 | tDATA | ||
Low-latency filter | See Table 3 | tDATA |
A minimum of 215 + 7 master clock periods must elapse before the device exits power-down mode to begin sampling, when in Frame-Sync interface mode, as shown in Figure 90 and Table 18. When using Frame-Sync interface mode, DOUT will read back low while the digital filter settles.
SYMBOL | DESCRIPTION | MIN | TYP | MAX | UNIT | |
---|---|---|---|---|---|---|
tw(PWDN) | Pulse duration RESET/PWDN low | 215 | tCLK | |||
td(PORS) | Frame-Sync Slave Mode, Delay time, RESET/PWDN rising edge to FSYNC rising edge | 215 + 7 | tCLK | |||
tsu(PORM) | Frame-Sync Slave Mode, Setup time, RESET/PWDN rising edge to CLK rising edge | 10 | ns | |||
td(PORM) | Frame-Sync Slave Mode, Delay time, CLK rising edge to FSYNC rising edge | 215 + 7 | tCLK | |||
td(NDR) | Delay time for new data to be ready | Wideband filters | 84 | tDATA | ||
Low-latency filter | See Table 3 | tDATA |
Data are retrieved from the ADS127L01 using a serial interface. To provide easy connection to either microcontrollers or DSPs, three communication modes are available: SPI, frame-sync master, and frame-sync slave. The FORMAT and FSMODE hardware mode pins select the interface. The same communication pins are used for all three interfaces: SCLK, DRDY/FSYNC, DIN, DAISYIN, and DOUT; however, functionality depends on the interface selected.
When FORMAT = 0, SPI interface is selected, and the DRDY/FSYNC pin becomes a data ready (DRDY) output. In SPI interface mode, commands and internal registers are available for further device configuration. Tie the FSMODE pin to DGND when using SPI communication mode.
When FORMAT = 1, frame-sync interface mode is selected, and the DRDY/FSYNC pin becomes an FSYNC input or output. Frame-sync offers two different modes controlled by the FSMODE pin.
When FSMODE = 0, the interface uses frame-sync slave mode, requiring that the SCLK and FSYNC signals are driven by the processor to the ADS127L01.
When FSMODE = 1, the interface is set to frame-sync master mode, and the SCLK and FSYNC signals are generated from the ADC derived from the master clock.
The SPI-compatible serial interface of the device is used to read conversion data, read and write the device configuration registers, and control device operation. Only SPI mode 1 (CPOL = 0, CPHA = 1) is supported. The interface consists of five control lines (CS, SCLK, DIN, DOUT, and DRDY/FSYNC), but the interface is operational with only four control lines. If the serial bus is not shared with any other device, CS can be tied low permanently so that only signals SCLK, DIN, DOUT and DRDY/FSYNC are required to communicate with the device.
Chip select (CS) is an active-low input that selects the device for SPI communication. CS must remain low for the entire duration of the serial communication to complete a command or data readback. When CS is taken high, the serial interface is reset, SCLK is ignored, and DOUT enters a high-impedance state. If the serial bus is not shared with another peripheral, CS can be tied low.
The serial clock (SCLK) features a Schmitt-triggered input, and is used to clock data into and out of the device on DIN and DOUT, respectively. SCLKs can be sent to the ADC continuously or in byte increments. Even though the input has hysteresis, keep the SCLK signal as clean as possible to prevent glitches from accidentally shifting data. When the serial interface is idle, hold SCLK low.
In SPI interface mode, DRDY/FSYNC is an active-low, new-data-ready indicator for when a new conversion result is ready for retrieval. When DRDY/FSYNC transitions low, new conversion data are ready. The DRDY/FSYNC signal transitions from low to high with the first SCLK falling edge, as shown in Figure 91. When no data are read during continuous conversion mode, DRDY/FSYNC remains low but pulses high for a duration of 2 · tCLK before the next DRDY/FSYNC falling edge. The DRDY/FSYNC pin is always actively driven, even when CS is high.
A new conversion result is loaded into the output shift register before DRDY transitions from high to low. The LSB of the previous data word must be read at least 4 · tCLK before the next DRDY falling edge. This delay is known as keep-out time (tKO). Keep SCLK low during tKO until the next conversion result is ready for retrieval, as shown in Figure 91.
The data input pin (DIN) is used with SCLK to send data (commands and register data) to the device. The device latches data on DIN on the SCLK falling edge. The device never drives the DIN pin.
DOUT is used with SCLK to read conversion and register data from the device. Data on DOUT are shifted out on the SCLK rising edge, to be read from the host on the SCLK falling edge. DOUT goes to a high-impedance state when CS is high.
DAISYIN is an optional pin used with SCLK to shift data in from a secondary ADS127L01 device when in a daisy-chain configuration. Data are shifted out from DOUT of a secondary device into the DAISYIN pin of the first device. The individual data bits are latched into DAISYIN on the SCLK falling edge. See the Multiple Device Configuration section for more information on using daisy-chain mode. If not used, tie the DAISYIN pin to DGND.
The ADS127L01 offers an SPI timeout feature that is used to recover communication when a serial interface transmission is interrupted. This feature is especially useful in applications where CS is permanently tied low and is not used to frame a communication sequence.
The timeout feature is disabled by default, but can be enabled in the CONFIG register. The time for the timeout to issue is also configurable using the CONFIG register. When enabled, and whenever a complete command is not sent within 214 · tCLK or 216 · tCLK (configurable by the TOUT_DEL bit in the CONFIG register), the serial interface resets and the next SCLK pulse starts a new communication cycle. For the RREG and WREG commands, a complete command includes the command byte plus the register bytes that are read or written.
The ADS127L01 provides flexible configuration, including commands and configurable registers, only when using the SPI interface. The commands, summarized in Table 19, are stand-alone and configure the operation of the ADS127L01. Each command is a single byte, except for the register read and write operations that require two or more bytes. CS must remain low for the entire command operation (especially for multibyte commands). Take CS high during a opcode command to abort the command.
COMMAND | DESCRIPTION | FIRST BYTE | SECOND BYTE |
---|---|---|---|
System Commands | |||
RESET | Reset the device | 0000 011x | |
START | Start or restart (synchronize) conversions | 0000 100x | |
STOP | Stop conversion | 0000 101x | |
Data Read Commands | |||
RDATA | Read data by command | 0001 0010 | |
Register Commands | |||
RREG | Read (nnnn + 1) registers starting at address rrrr | 0010 rrrr | 0000 nnnn |
WREG | Write (nnnn + 1) registers starting at address rrrr | 0100 rrrr | 0000 nnnn |
The RESET command halts conversions and resets the ADC to power-on-reset values. During this time, the digital filter resets, requiring an additional power-up time for conversions to begin. The RESET command is decoded by the ADS127L01 on the seventh falling edge of SCLK. For more information, refer to the Reset and Power-Down Pin (RESET/PWDN) section.
The START command starts conversions and resynchronize the device. When conversions are stopped, either at power-up or following a STOP command, issue a START command to begin ADC conversions. Issuing a START command restarts the conversions by resetting the digital filters. During the reset period, DRDY/FSYNC does not toggle. The START command is decoded by the ADS127L01 on the seventh falling edge of SCLK. The START pin must be held low if the START and STOP commands are used. For more information, refer to the Start Pin (START) section.
The STOP command places the ADC in an idle state where the modulator stops converting. The STOP command is decoded by the ADS127L01 on the seventh falling edge of SCLK. The START pin must be held low if the START and STOP commands are used.
The RDATA command reloads the output shift register to the MSB of the most recent data. The RDATA command is decoded on the eighth SCLK falling edge, and begins shifting out the MSB of the data word on DOUT on the ninth SCLK.
The RREG command reads the number of bytes specified by nnnn (number of registers to be read – 1) from the device configuration register, starting at register address rrrr. The command is completed after nnnn + 1 bytes are clocked out after the RREG command byte. For example, the command to read three registers (nnnn = 0010) starting at register address 00h (rrrr = 0000) is 0010 0000 0000 0010 as shown in Figure 92. The communication length must be extended by the proper number of SCLKs to shift register contents out.
The wREG command writes the number of bytes specified by nnnn (number of registers to be written – 1) to the device configuration register, starting at register address rrrr. The command is completed after nnnn + 1 bytes are clocked in after the WREG command byte. For example, the command to write two registers (nnnn = 0001) starting at register address 01h (rrrr = 0001) is 0100 0001 0000 0001 as shown in Figure 93. Two bytes follow the command to write the contents to the registers. The frame must extend by the proper number of SCLKs to write data to the registers.
Frame-sync interface is similar to the interface often used on audio ADCs. The ADS127L01 offers both frame-sync master and frame-sync slave modes that are selectable using the FSMODE pin. In frame-sync format, commands and register assignments are not available. Tie DIN low to DGND.
When operating in frame-sync master mode, the ADC acts as the system master, and provides the FSYNC, SCLK, and DOUT signals. The FSYNC and SCLK signals are derived as a function of the master clock input, fCLK. The data are output MSB first on the rising edge of FSYNC.
CS is not used in frame-sync interface mode.. Tie the CS pin to DGND.
When operating in frame-sync master mode, the serial clock (SCLK) is derived from the master clock and provided from the ADC to the microprocessor. Every frame period, tc(FRAME), includes 32 SCLKs to shift all data out before new data are ready. This SCLK speed is proportional to the frame size, tc(FRAME) / 32 in frame-sync master mode. The frame size is determined by the data rate setting using the hardware FILTER pin settings, OSR pin settings, and speed of the master clock, fCLK. The data on DOUT are clocked out on the falling edge of SCLK to be latched by the host processor on the rising edge of SCLK.
In frame-sync master mode, the FSYNC pin is an output whose period is proportional to the ADC programmed data rate. Within each FSYNC period are 32 SCLKs to shift out the data on DOUT. The FSYNC duty cycle is designed to be 50-50, where an FSYNC low-to-high transition takes place before the MSB of new data, and high-to-low transition takes place before bit 15 on the falling edge of SCLK. For more information on FSYNC master-mode timing, see the Frame-Sync Master Mode Timing Requirements.
DIN is not available in frame-sync master mode. Tie DIN to DGND.
The conversion data are clocked out on the falling edge of SCLK to be latched by the host processor on the rising edge of SCLK. The MSB data become valid on DOUT after FSYNC goes high. The subsequent bits are shifted out with each falling edge of SCLK.
DAISYIN and daisy-chain operation are not supported in frame-sync master mode. Tie DAISYIN to DGND.
When operating in frame-sync slave mode, the user must supply the framing signal FSYNC (similar to the left/right clock on stereo audio ADCs) and the serial clock SCLK (similar to the bit clock on audio ADCs). The data are output MSB first or left-justified on the rising edge of FSYNC. The FSYNC and SCLK inputs must be continuously running with the relationships shown in the Frame-Sync Timing Requirements.
CS is not used in frame-sync programming. Tie CS to DGND.
In frame-sync slave mode, use SCLK to clock data out on DOUT. SCLK must run continuously; if SCLK is shut down, the data read back is corrupted. The number of SCLKs within a frame period (tc(FRAME)) can be any power-of-two ratio of CLK cycles (1, 1/2, 1/4, and so on), as long as the number of cycles is sufficient to shift the data output within one frame.
Use SCLK to also shift data into DAISYIN when multiple devices are configured for daisy-chain operation. Even though SCLK has hysteresis, keep SCLK as clean as possible to prevent glitches from accidentally shifting the data.
In frame-sync slave mode, the FSYNC pin is an input that transitions low to high at the data-rate frequency. The required number of fCLK cycles to each FSYNC period depends on the configuration of the FILTER[1:0] and OSR[1:0] pins. If the FSYNC period is not the proper value, data read back is corrupted. For more information on frame-sync slave-mode timing, see the Frame-Sync Slave Mode Timing Requirements.
DIN is not used in frame-sync slave mode. Tie the DIN pin to DGND.
The conversion data are clocked out on the falling edge of SCLK to be latched by the host processor on the rising edge of SCLK. The MSB data become valid on DOUT after FSYNC goes high. The subsequent bits are shifted out with each falling edge of SCLK.
DAISYIN is an optional pin used along with SCLK to shift data from a secondary ADS127L01 device. Data are shifted out from DOUT of a secondary device into the DAISYIN pin of the first device. The data on DOUT is latched into DAISYIN on the SCLK falling edge. See the Multiple Device Configuration section for more information on using daisy-chain mode. Tie the DAISYIN pin to DGND if not used.
The ADS127L01 provides either a 24-bit or 32-bit output word, 24 bits of which are data in binary twos complement format with an optional eight LSBs containing status word information. The size of one code (LSB) is calculated using Equation 8:
A positive full-scale input [VIN ≥ (+FS – 1 LSB) = (VREF – 1 LSB)] produces an output code of 7FFFFFh, and a negative full-scale input (VIN ≤ –FS = –VREF ) produces an output code of 800000h. The output clips at these codes for signals that exceed full-scale.
Table 20 summarizes the ideal output codes for different input signals.
INPUT SIGNAL, VIN
(VAINP – VAINN) |
IDEAL OUTPUT CODE(1) |
---|---|
≥ +FS (223 – 1) / 223 | 7FFFFFh |
+FS / 223 | 000001h |
0 | 0 |
–FS / 223 | FFFFFFh |
≤ –FS | 800000h |
Trailing the 24 bits of data is an optional 8-bit status word. The status word provides a real-time update of internal system monitors and data integrity. By default, the contents are a mixture of 4-bit CRC data integrity and system monitors. Alternatively, the status word can be set to output an 8-bit CRC without the system monitors. The CRCB bit in the CONFIG regsiter controls the status word contents. Set the CRCB bit to 0 for the status word to contain 4-bit CRC [bits 7:4], one bit [bit 3] to monitor out of range input (INP), and three bits [bits 2:0] to read back as 0. Set the CRCB bit to 1 for all eight bits [bits 7:0] of the status word to contain 8-bit CRC. See Figure 94 for a visual representation of the two modes.
By default, the optional 8-bit status word is enabled, but can be disabled when operating in SPI interface mode and setting the CS_ENB bit to 1 in the CONFIG register.
The ADS127L01 implements two standard CRC algorithms: CRC-4-ITU to provide a 4-bit CRC, and CRC-8-CCITT for an 8-bit CRC. By default, the CRC-4-ITU option is enabled. Set the CRCB bit to 1 in the CONFIG register to change the format to CRC-8-CCITT and remove the system monitor bits from the status word.
The CRC is placed after the ADC data. The CRC is calculated using only the ADC output. When the 4-bit CRC is enabled, the ADS127L01 outputs a 4-bit status block after the CRC that is not used as part of the CRC check.
To calculate the CRC, divide the data bytes by the CRC polynomial using an XOR operation.
In 4-bit CRC mode, the CRC value is the 4-bit remainder of the division of the data bytes by a CRC polynomial of P(x) = x4 + x + 1.
In 8-bit CRC mode, the CRC value is the 8-bit remainder of the division of the ADC data bytes by a CRC polynomial of P(x) = x8 + x2 + x + 1.
Then compare the calculated CRC values to the provided CRC value in the ADC output.
If the values do not match, a data-transmission error has occurred. In the event of a data-transmission error, read the data again. The CRC provides a higher level of detection of multiple-bit errors.
The following list shows a general procedure to compute the CRC value. Assume the shift register is n bits wide, where n is the number of CRC bits:
NOTE
The CRC algorithm used here employs an assumed set high bit. This bit is divided out by left-shifting the bit out of the register prior to XORing with the polynomial shift register. This process allows for calculation of the CRC with 8-bit hardware.
Table 21 describes the various ADS127L01 registers. Access to the registers is available in SPI interface mode. Register access is not available in frame-sync master or slave interface modes.
ADDRESS | REGISTER | RESET VALUE (Hex) | BIT 7 | BIT 6 | BIT 5 | BIT 4 | BIT 3 | BIT 2 | BIT 1 | BIT 0 |
---|---|---|---|---|---|---|---|---|---|---|
Device ID (Read-Only Registers) | ||||||||||
00h | ID | x3h(1) | REV_ID[4:0] | DEV_ID[2:0] | ||||||
Configuration Settings | ||||||||||
01h | CONFIG | 00h | 0 | 0 | FSC | OFC | TOUT_DEL | SPI_TOUT | CS_ENB | CRCB |
02h | OFC0 | 00h | OFC_B[7:0] | |||||||
03h | OFC1 | 00h | OFC_B[15:8] | |||||||
04h | OFC2 | 00h | OFC_B[23:16] | |||||||
05h | FSC0 | 00h | FSC_B[7:0] | |||||||
06h | FSC1 | 80h | FSC_B[15:8] | |||||||
Device Settings (Read-Only Registers) | ||||||||||
07h | MODE | xx(1) | 0 | HR | OSR[1:0] | OSR[1:0] | FILTER[1:0] | FILTER[1:0] | FORMAT | FSMODE |
This register is programmed during device manufacture to indicate device characteristics.
7 | 6 | 5 | 4 | 3 | 2 | 1 | 0 |
REV_ID[4:0] | DEV_ID[2:0] | ||||||
R-Undefined(1) | R-3h |
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset |
Bit | Field | Type | Reset | Description |
---|---|---|---|---|
7:3 | REV_ID[4:0] | R | xh(1) | Revision ID. These bits indicate the revision of the device and are subject to change without notice. |
2:0 | DEV_ID[2:0] | R | 3h | Device Family Identification.
011 = ADS127L01 |
This register contains the software controlled device options.
7 | 6 | 5 | 4 | 3 | 2 | 1 | 0 |
0 | 0 | FSC | OFC | TOUT_DEL | SPI_TOUT | CS_ENB | CRCB |
R-0h | R-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h |
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset |
Bit | Field | Type | Reset | Description |
---|---|---|---|---|
7:6 | Reserved | R | 0h | Reserved
Always write 0 |
5 | FSC | R/W | 0h | System Gain Correction
This bit enables system gain correction using the register contents from FSC0 and FSC1 registers. 0 = Disable system gain correction 1 = Enable system gain correction |
4 | OFC | R/W | 0h | Offset Correction
This bit enables Offset Correction using the register contents from OFC0, OFC1, and OFC2 registers. 0 = Disable offset correction 1 = Enable offset correction |
3 | TOUT_DEL | R/W | 0h | SPI Timeout
This bit sets the time limit to hold SCLK in an idle position for the SPI reset. 0 = SPI timeout delay set to 216 tCLK. 1 = SPI timeout delay set to 214 tCLK. |
2 | SPI_TOUT | R/W | 0h | SPI Timeout Enable
This bit enables or disables the SPI timeout function. 0 = Disable SPI timeout 1 = Enable SPI timeout |
1 | CS_ENB | R/W | 0h | Status Word Enable
This bit enables or disables the status word that is present following the 24-bit data output. 0 = Enable status word 1 = Disable status word |
0 | CRCB | R/W | 0h | Status Word Contents
This bit sets the contents used in the status word. 0 = CRC-4 and 4 bits of ADC diagnostics 1 = CRC-8 |
This register contains the least significant byte for the system offset calibration. The system offset calibration is a total of three bytes or 24 bits.
7 | 6 | 5 | 4 | 3 | 2 | 1 | 0 |
OFC_B[7:0] | |||||||
R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h |
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset |
Bit | Field | Type | Reset | Description |
---|---|---|---|---|
7:0 | OFC_B[7:0] | R/W | 00h | Offset Correction Bits
These bits set the system offset error correction. |
This register contains the middle byte for the system offset calibration. The system offset calibration is a total of three bytes or 24 bits.
7 | 6 | 5 | 4 | 3 | 2 | 1 | 0 |
OFC_B[15:8] | |||||||
R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h |
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset |
Bit | Field | Type | Reset | Description |
---|---|---|---|---|
7:0 | OFC_B[15:8] | R/W | 00h | Offset Correction Bits
These bits set the system offset error correction. |
This register contains the most significant byte for the system offset calibration. The system offset calibration is a total of three bytes or 24 bits.
7 | 6 | 5 | 4 | 3 | 2 | 1 | 0 |
OFC_B[23:16] | |||||||
R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h |
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset |
Bit | Field | Type | Reset | Description |
---|---|---|---|---|
7:0 | OFC_B[23:16] | R/W | 00h | Offset Correction Bits
These bits set the system offset error correction. |
This register contains the least significant byte for the system gain calibration. The system gain calibration is a total of two bytes or 16 bits.
7 | 6 | 5 | 4 | 3 | 2 | 1 | 0 |
FSC_B[7:0] | |||||||
R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h |
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset |
Bit | Field | Type | Reset | Description |
---|---|---|---|---|
7:0 | FSC_B[7:0] | R/W | 00h | Gain Correction Bits
These bits set the system gain calibration value. |
This register contains the most significant byte for the system gain calibration. The system gain calibration is a total of two bytes or 16 bits.
7 | 6 | 5 | 4 | 3 | 2 | 1 | 0 |
FSC_B[15:8] | |||||||
R/W-1h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h | R/W-0h |
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset |
Bit | Field | Type | Reset | Description |
---|---|---|---|---|
7:0 | FSC_B[15:8] | R/W | 80h | Gain Correction Bits
These bits set the system gain calibration value. |
This register displays the hardware bit settings.
7 | 6 | 5 | 4 | 3 | 2 | 1 | 0 |
0 | HR | OSR[1:0] | FILTER[1:0] | FORMAT | FSMODE | ||
R-0h | R-xh | R-xh | R-xh | R-xh | R-xh | R-xh | R-xh |
LEGEND: R/W = Read/Write; R = Read only; -n = value after reset |
Bit | Field | Type | Reset | Description |
---|---|---|---|---|
7 | RESERVED | R | 0h | Reserved
Always reads 0 |
6 | HR | R | xh | High-Resolution Setting
This bit shows the readback status of HR (pin 29) 0 = LP Mode 1 = HR mode |
5:4 | OSR[1:0] | R | xh | OSR Setting
This bit shows the readback status of OSR1 (pin 15) and OSR2 (pin 16) If FILTER[1:0] = 00 or 01 (Wideband filters): 00 = 32 01 = 64 10 = 128 11 = 256 If FILTER[1:0] = 10 (Low-latency filter): 00 = 32 01 = 128 10 = 512 11 = 2048 |
3:2 | FILTER[1:0] | R | xh | Filter Option Setting
This bit shows the readback status of FILTER1 (pin 12) and FILTER0 (pin 13) Digital-filter mode select: 00 = Wideband 1 filter 01 = Wideband 2 filter 10 = Low-latency filter (SINC5 and SINC) 11 = Reserved |
1 | FORMAT | R | xh | Interface Mode Setting
This bit shows the readback status of FORMAT (pin 30) 0 = SPI interface mode 1 = Frame-sync interface mode |
0 | FSMODE | R | xh | Frame-sync mode setting
This bit shows the readback status of FSMODE (pin 14) 0 = Frame-sync slave interface mode 1 = Frame-sync master interface mode |