TPS56x210A、4.5V～17V入力、2A、3A同期整流降圧型レギュレータ 8ピンSOT-23パッケージ

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6.7.1 TPS562210A Characteristics

V_IN = 12 V (unless otherwise noted)

Figure 1. Supply Current vs Junction Temperature

Figure 3. VFB Voltage vs Junction Temperature

Figure 5. Efficiency vs Output Current

Figure 7. Switching Frequency vs Input Voltage

Figure 2. VIN Shutdown Current vs Junction Temperature

Figure 4. EN Current vs EN Voltage

VI = 5 V

Figure 6. Efficiency vs Output Current

Figure 8. Switching Frequency vs Output Current

6.7.2 TPS563210A Characteristics

V_IN = 12V (unless otherwise noted)

Figure 9. Supply Current vs Junction Temperature

Figure 11. VFB Voltage vs Junction Temperature

Figure 13. Efficiency vs Output Current

Figure 15. Switching Frequency vs Input Voltage

Figure 10. VIN Shutdown Current vs Junction Temperature

Figure 12. EN Current vs EN Voltage

VI = 5 V

Figure 14. Efficiency vs Output Current

Figure 16. Switching Frequency vs Output Current

7.3.1 The Adaptive On-Time Control and PWM Operation

The main control loop of the TPS562210A and TPS563210A are adaptive on-time pulse width modulation (PWM) controller that supports a proprietary D-CAP2™ mode control. The D-CAP2™ mode control combines adaptive on-time control with an internal compensation circuit for pseudo-fixed frequency and low external component count configuration with both low ESR and ceramic output capacitors. It is stable even with virtually no ripple at the output.

At the beginning of each cycle, the high-side MOSFET is turned on. This MOSFET is turned off after internal one shot timer expires. This one shot duration is set proportional to the converter input voltage, VIN, and inversely proportional to the output voltage, V_O, to maintain a pseudo-fixed frequency over the input voltage range, hence it is called adaptive on-time control. The one-shot timer is reset and the high-side MOSFET is turned on again when the feedback voltage falls below the reference voltage. An internal ramp is added to reference voltage to simulate output ripple, eliminating the need for ESR induced output ripple from D-CAP2™ mode control.

7.3.2 Soft Start and Pre-Biased Soft Start

The TPS562210A and TPS563210A have adjustable soft-start. When the EN pin becomes high, the SS charge current (I_SS) begins charging the capacitor which is connected from the SS pin to GND (C_SS). Smooth control of the output voltage is maintained during start up. The equation for the soft start time, Tss is shown in Equation 1.

Equation 1.

where V_FBTH is 0.765 V and Iss is 6 µA.

If the output capacitor is pre-biased at startup, the devices initiate switching and start ramping up only after the internal reference voltage becomes greater than the feedback voltage V_FB. This scheme ensures that the converters ramp up smoothly into regulation point.

7.3.3 Power Good

The power good output, PG is an open drain output. The power good function becomes active after 1.7 times soft-start time. When the output voltage becomes within –10% of the target value, internal comparators detect power good state and the power good signal becomes high. If the feedback voltage goes under 15% of the target value, the power good signal becomes low.

7.3.4 Current Protection

The output over-current limit (OCL) is implemented using a cycle-by-cycle valley detect control circuit. The switch current is monitored during the OFF state by measuring the low-side FET drain to source voltage. This voltage is proportional to the switch current. To improve accuracy, the voltage sensing is temperature compensated.

During the on time of the high-side FET switch, the switch current increases at a linear rate determined by V_IN, V_OUT, the on-time and the output inductor value. During the on time of the low-side FET switch, this current decreases linearly. The average value of the switch current is the load current I_OUT. If the monitored current is above the OCL level, the converter maintains low-side FET on and delays the creation of a new set pulse, even the voltage feedback loop requires one, until the current level becomes OCL level or lower. In subsequent switching cycles, the on-time is set to a fixed value and the current is monitored in the same manner. If the over current condition exists consecutive switching cycles, the internal OCL threshold is set to a lower level, reducing the available output current. When a switching cycle occurs where the switch current is not above the lower OCL threshold, the counter is reset and the OCL threshold is returned to the higher value.

There are some important considerations for this type of over-current protection. The load current is higher than the over-current threshold by one half of the peak-to-peak inductor ripple current. Also, when the current is being limited, the output voltage tends to fall as the demanded load current may be higher than the current available from the converter. This may cause the output voltage to fall. When the VFB voltage falls below the UVP threshold voltage, the UVP comparator detects it. And then, the device will shut down after the UVP delay time (typically 14 µs) and re-start after the hiccup time.

When the over current condition is removed, the output voltage returns to the regulated value.

7.3.5 Over Voltage Protection

TPS562210A and TPS563210A detect over voltage condition by monitoring the feedback voltage (VFB). When the feedback voltage becomes higher than 125% of the target voltage, the OVP comparator output goes high and the high-side MOSFET is turns off. This function is non-latch operation.

7.3.6 UVLO Protection

Under voltage lock out protection (UVLO) monitors the internal regulator voltage. When the voltage is lower than UVLO threshold voltage, the device is shut off. This protection is non-latching.

7.3.7 Thermal Shutdown

The device monitors the temperature of itself. If the temperature exceeds the threshold value (typically 155°C), the device is shut off. This is a non-latch protection.

7.4.1 Advanced Eco-Mode™ Control

The TPS562210A and TPS563210A are designed with Advanced Eco-mode™ to maintain high light load efficiency. As the output current decreases from heavy load condition, the inductor current is also reduced and eventually comes to point that its rippled valley touches zero level, which is the boundary between continuous conduction and discontinuous conduction modes. The rectifying MOSFET is turned off when the zero inductor current is detected. As the load current further decreases the converter runs into discontinuous conduction mode. The on-time is kept almost the same as it was in the continuous conduction mode so that it takes longer time to discharge the output capacitor with smaller load current to the level of the reference voltage. This makes the switching frequency lower, proportional to the load current, and keeps the light load efficiency high. The transition point to the light load operation I_OUT(LL) current can be calculated in Equation 2.

Equation 2.